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matlab/detail_control_1_complementary_filtering.m

@@ -69,21 +69,108 @@ H1 = 1 - H2;
 % The function generateCF can also be used to synthesize the complementary filters.
 % [H1, H2] = generateCF(W1, W2);
 
-%% Bode plot of the Weighting filters and Obtained complementary filters
+%% Bode plot of the obtained complementary filters
 figure;
+tiledlayout(3, 1, 'TileSpacing', 'Compact', 'Padding', 'None');
+
+% Magnitude
+ax1 = nexttile([2, 1]);
 hold on;
-plot(freqs, 1./abs(squeeze(freqresp(W1, freqs, 'Hz'))), '--', 'color', colors(1,:),'DisplayName', '$|W_1|^{-1}$');
+set(gca,'ColorOrderIndex',1)
-plot(freqs, 1./abs(squeeze(freqresp(W2, freqs, 'Hz'))), '--', 'color', colors(2,:),'DisplayName', '$|W_2|^{-1}$');
+plot(freqs, 1./abs(squeeze(freqresp(W1, freqs, 'Hz'))), '--', 'DisplayName', '$|W_1|^{-1}$');
-plot(freqs,    abs(squeeze(freqresp(H1, freqs, 'Hz'))), '-',  'color', [colors(1,:), 0.5], 'linewidth', 2.5,'DisplayName', '$H_1$');
+set(gca,'ColorOrderIndex',2)
-plot(freqs,    abs(squeeze(freqresp(H2, freqs, 'Hz'))), '-',  'color', [colors(2,:), 0.5], 'linewidth', 2.5,'DisplayName', '$H_2$');
+plot(freqs, 1./abs(squeeze(freqresp(W2, freqs, 'Hz'))), '--', 'DisplayName', '$|W_2|^{-1}$');
+
+set(gca,'ColorOrderIndex',1)
+plot(freqs, abs(squeeze(freqresp(H1, freqs, 'Hz'))), '-', 'DisplayName', '$H_1$');
+set(gca,'ColorOrderIndex',2)
+plot(freqs, abs(squeeze(freqresp(H2, freqs, 'Hz'))), '-', 'DisplayName', '$H_2$');
 hold off;
 set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
+set(gca, 'XTickLabel',[]); ylabel('Magnitude');
 ylim([8e-4, 20]);
-xlim([freqs(1), freqs(end)]);
+yticks([1e-3, 1e-2, 1e-1, 1, 1e1]);
+yticklabels({'', '$10^{-2}$', '', '$10^0$', ''})
 leg = legend('location', 'south', 'FontSize', 8, 'NumColumns', 2);
 leg.ItemTokenSize(1) = 18;
 
+% Phase
+ax2 = nexttile;
+hold on;
+set(gca,'ColorOrderIndex',1)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H1, freqs, 'Hz'))), '-');
+set(gca,'ColorOrderIndex',2)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H2, freqs, 'Hz'))), '-');
+hold off;
+set(gca, 'XScale', 'log');
+xlabel('Frequency [Hz]'); ylabel('Phase [deg]');
+yticks([-180:90:180]);
+ylim([-180, 200])
+yticklabels({'-180', '', '0', '', '180'})
+
+linkaxes([ax1,ax2],'x');
+xlim([freqs(1), freqs(end)]);
+
+%% Design of "Closed-loop" complementary filters
+% Design of the Weighting Functions
+W1 = generateWF('n', 3, 'w0', 2*pi*10, 'G0', 1000, 'Ginf', 1/10, 'Gc', 0.45);
+W2 = generateWF('n', 2, 'w0', 2*pi*10, 'G0', 1/10, 'Ginf', 1000, 'Gc', 0.45);
+
+% Generalized plant for "closed-loop" complementary filter synthesis
+P = [ W1 0   1;
+     -W1 W2 -1];
+
+% Standard H-Infinity Synthesis
+[L, ~, gamma, ~] = hinfsyn(P, 1, 1,'TOLGAM', 0.001, 'METHOD', 'ric', 'DISPLAY', 'on');
+
+% Complementary filters
+H1 = inv(1 + L);
+H2 = 1 - H1;
+
+%% Bode plot of the obtained complementary filters after H-infinity mixed-sensitivity synthesis
+figure;
+tiledlayout(3, 1, 'TileSpacing', 'Compact', 'Padding', 'None');
+
+% Magnitude
+ax1 = nexttile([2, 1]);
+hold on;
+set(gca,'ColorOrderIndex',1)
+plot(freqs, 1./abs(squeeze(freqresp(W1, freqs, 'Hz'))), '--', 'DisplayName', '$|W_1|^{-1}$');
+set(gca,'ColorOrderIndex',2)
+plot(freqs, 1./abs(squeeze(freqresp(W2, freqs, 'Hz'))), '--', 'DisplayName', '$|W_2|^{-1}$');
+
+set(gca,'ColorOrderIndex',1)
+plot(freqs, abs(squeeze(freqresp(H1, freqs, 'Hz'))), '-', 'DisplayName', '$H_1$');
+set(gca,'ColorOrderIndex',2)
+plot(freqs, abs(squeeze(freqresp(H2, freqs, 'Hz'))), '-', 'DisplayName', '$H_2$');
+
+plot(freqs, abs(squeeze(freqresp(L, freqs, 'Hz'))), 'k--', 'DisplayName', '$|L|$');
+hold off;
+set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
+set(gca, 'XTickLabel',[]); ylabel('Magnitude');
+ylim([1e-3, 1e3]);
+yticks([1e-3, 1e-2, 1e-1, 1, 1e1, 1e2, 1e3]);
+yticklabels({'', '$10^{-2}$', '', '$10^0$', '', '$10^2$', ''});
+leg = legend('location', 'northeast', 'FontSize', 8, 'NumColumns', 3);
+leg.ItemTokenSize(1) = 18;
+
+% Phase
+ax2 = nexttile;
+hold on;
+set(gca,'ColorOrderIndex',1)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H1, freqs, 'Hz'))), '-');
+set(gca,'ColorOrderIndex',2)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H2, freqs, 'Hz'))), '-');
+hold off;
+set(gca, 'XScale', 'log');
+xlabel('Frequency [Hz]'); ylabel('Phase [deg]');
+yticks([-180:90:180]);
+ylim([-180, 200])
+yticklabels({'-180', '', '0', '', '180'})
+
+linkaxes([ax1,ax2],'x');
+xlim([freqs(1), freqs(end)]);
+
 %% Synthesis of a set of three complementary filters
 % Design of the Weighting Functions
 W1 = generateWF('n', 2, 'w0', 2*pi*1, 'G0', 1/10, 'Ginf', 1000, 'Gc', 0.5);
@@ -108,16 +195,45 @@ H1 = 1 - H2 - H3;
 
 %% Bode plot of the inverse weighting functions and of the three complementary filters obtained using the H-infinity synthesis
 figure;
+tiledlayout(3, 1, 'TileSpacing', 'Compact', 'Padding', 'None');
+
+% Magnitude
+ax1 = nexttile([2, 1]);
 hold on;
-plot(freqs, 1./abs(squeeze(freqresp(W1, freqs, 'Hz'))), '--', 'color', colors(1,:),'DisplayName', '$|W_1|^{-1}$');
+set(gca,'ColorOrderIndex',1)
-plot(freqs, 1./abs(squeeze(freqresp(W2, freqs, 'Hz'))), '--', 'color', colors(2,:),'DisplayName', '$|W_2|^{-1}$');
+plot(freqs, 1./abs(squeeze(freqresp(W1, freqs, 'Hz'))), '--', 'DisplayName', '$|W_1|^{-1}$');
-plot(freqs, 1./abs(squeeze(freqresp(W3, freqs, 'Hz'))), '--', 'color', colors(3,:),'DisplayName', '$|W_3|^{-1}$');
+set(gca,'ColorOrderIndex',2)
-plot(freqs,    abs(squeeze(freqresp(H1, freqs, 'Hz'))), '-',  'color', [colors(1,:), 0.5], 'linewidth', 2.5,'DisplayName', '$H_1$');
+plot(freqs, 1./abs(squeeze(freqresp(W2, freqs, 'Hz'))), '--', 'DisplayName', '$|W_2|^{-1}$');
-plot(freqs,    abs(squeeze(freqresp(H2, freqs, 'Hz'))), '-',  'color', [colors(2,:), 0.5], 'linewidth', 2.5,'DisplayName', '$H_2$');
+set(gca,'ColorOrderIndex',3)
-plot(freqs,    abs(squeeze(freqresp(H3, freqs, 'Hz'))), '-',  'color', [colors(3,:), 0.5], 'linewidth', 2.5,'DisplayName', '$H_3$');
+plot(freqs, 1./abs(squeeze(freqresp(W3, freqs, 'Hz'))), '--', 'DisplayName', '$|W_3|^{-1}$');
+set(gca,'ColorOrderIndex',1)
+plot(freqs, abs(squeeze(freqresp(H1, freqs, 'Hz'))), '-', 'DisplayName', '$H_1$');
+set(gca,'ColorOrderIndex',2)
+plot(freqs, abs(squeeze(freqresp(H2, freqs, 'Hz'))), '-', 'DisplayName', '$H_2$');
+set(gca,'ColorOrderIndex',3)
+plot(freqs, abs(squeeze(freqresp(H3, freqs, 'Hz'))), '-', 'DisplayName', '$H_3$');
+set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
 hold off;
 set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
+ylabel('Magnitude');
-xlim([freqs(1), freqs(end)]); ylim([1e-4, 20]);
+set(gca, 'XTickLabel',[]);
-leg = legend('location', 'southeast', 'FontSize', 8);
+ylim([1e-4, 20]);
+leg = legend('location', 'northeast', 'FontSize', 8);
 leg.ItemTokenSize(1) = 18;
+
+% Phase
+ax2 = nexttile;
+hold on;
+set(gca,'ColorOrderIndex',1)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H1, freqs, 'Hz'))));
+set(gca,'ColorOrderIndex',2)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H2, freqs, 'Hz'))));
+set(gca,'ColorOrderIndex',3)
+plot(freqs, 180/pi*phase(squeeze(freqresp(H3, freqs, 'Hz'))));
+hold off;
+xlabel('Frequency [Hz]'); ylabel('Phase [deg]');
+set(gca, 'XScale', 'log');
+yticks([-180:90:180]); ylim([-220, 220]);
+
+linkaxes([ax1,ax2],'x');
+xlim([freqs(1), freqs(end)]);

matlab/detail_control_2_decoupling.m

@@ -1,248 +0,0 @@
-%% Clear Workspace and Close figures
-clear; close all; clc;
-
-%% Intialize Laplace variable
-s = zpk('s');
-
-%% Path for functions, data and scripts
-addpath('./src/'); % Path for functions
-
-%% Colors for the figures
-colors = colororder;
-
-%% Initialize Frequency Vector
-freqs = logspace(0, 3, 1000);
-
-%% Compute Equation of motion
-l = 1; h=2;
-la = 0.5; % Horizontal position of actuators [m]
-ha = 0.2; % Vertical of actuators [m]
-
-m = 40; % Payload mass [kg]
-I = 5; % Payload rotational inertia [kg m^2]
-
-c = 2e2; % Actuator Damping [N/(m/s)]
-k = 1e6; % Actuator Stiffness [N/m]
-
-% Unit vectors of the actuators
-s1 = [1;0];
-s2 = [0;1];
-s3 = [0;1];
-
-% Stiffnesss and Damping matrices of the struts
-Kr = diag([k,k,k]);
-Cr = diag([c,c,c]);
-
-%  Location of the joints with respect to the center of mass
-Mb1 = [-l/2;-ha];
-Mb2 = [-la; -h/2];
-Mb3 = [ la; -h/2];
-
-% Jacobian matrix (Center of Mass)
-J_CoM = [s1', Mb1(1)*s1(2)-Mb1(2)*s1(1);
-         s2', Mb2(1)*s2(2)-Mb2(2)*s2(1);
-         s3', Mb3(1)*s3(2)-Mb3(2)*s3(1)];
-
-% Mass Matrix in frame {M}
-M = diag([m,m,I]);
-
-% Stiffness Matrix in frame {M}
-K = J_CoM'*Kr*J_CoM;
-
-% Damping Matrix in frame {M}
-C = J_CoM'*Cr*J_CoM;
-
-% Plant in the frame of the struts
-G_L = J_CoM*inv(M*s^2 + C*s + K)*J_CoM';
-
-figure;
-tiledlayout(3, 3, 'TileSpacing', 'Compact', 'Padding', 'None');
-
-for out_i = 1:3
-    for in_i = 1:3
-        nexttile;
-        plot(freqs, abs(squeeze(freqresp(G_L(out_i,in_i), freqs, 'Hz'))), 'k-', ...
-             'DisplayName', sprintf('$\\mathcal{L}_%i/\\tau_%i$', out_i, in_i));
-        set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-        xlim([freqs(1), freqs(end)]); ylim([2e-8, 4e-5]);
-        xticks([1e0, 1e1, 1e2])
-        yticks([1e-7, 1e-6, 1e-5])
-        leg = legend('location', 'northeast', 'FontSize', 8);
-        leg.ItemTokenSize(1) = 18;
-
-        if in_i == 1
-            ylabel('Mag. [m/N]')
-        else
-            set(gca, 'YTickLabel',[]);
-        end
-
-        if out_i == 3
-            xlabel('Frequency [Hz]')
-        else
-            set(gca, 'XTickLabel',[]);
-        end
-    end
-end
-
-%% Jacobian Decoupling - Center of Mass
-G_CoM = pinv(J_CoM)*G_L*pinv(J_CoM');
-G_CoM.InputName  = {'Fx', 'Fy', 'Mz'};
-G_CoM.OutputName  = {'Dx', 'Dy', 'Rz'};
-
-figure;
-hold on;
-plot(freqs, abs(squeeze(freqresp(G_CoM(1, 3), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-     'DisplayName', '$D_{x,\{M\}}/M_{z,\{M\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoM(3, 1), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-     'DisplayName', '$R_{z,\{M\}}/F_{x,\{M\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoM(1, 1), freqs, 'Hz'))), 'color', colors(1,:), 'DisplayName', '$D_{x,\{M\}}/F_{x,\{M\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoM(2, 2), freqs, 'Hz'))), 'color', colors(2,:), 'DisplayName', '$D_{y,\{M\}}/F_{y,\{M\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoM(3, 3), freqs, 'Hz'))), 'color', colors(3,:), 'DisplayName', '$R_{z,\{M\}}/M_{z,\{M\}}$');
-hold off;
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-ylim([1e-10, 1e-3]);
-leg = legend('location', 'southwest', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;
-
-%% Jacobian Decoupling - Center of Mass
-%  Location of the joints with respect to the center of stiffness
-Mb1 = [-l/2; 0];
-Mb2 = [-la; -h/2+ha];
-Mb3 = [ la; -h/2+ha];
-
-% Jacobian matrix (Center of Stiffness)
-J_CoK = [s1', Mb1(1)*s1(2)-Mb1(2)*s1(1);
-         s2', Mb2(1)*s2(2)-Mb2(2)*s2(1);
-         s3', Mb3(1)*s3(2)-Mb3(2)*s3(1)];
-
-G_CoK = pinv(J_CoK)*G_L*pinv(J_CoK');
-G_CoK.InputName   = {'Fx', 'Fy', 'Mz'};
-G_CoK.OutputName  = {'Dx', 'Dy', 'Rz'};
-
-figure;
-hold on;
-plot(freqs, abs(squeeze(freqresp(G_CoK(1, 1), freqs, 'Hz'))), 'color', colors(1,:), 'DisplayName', '$D_{x,\{K\}}/F_{x,\{K\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoK(2, 2), freqs, 'Hz'))), 'color', colors(2,:), 'DisplayName', '$D_{y,\{K\}}/F_{y,\{K\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoK(3, 3), freqs, 'Hz'))), 'color', colors(3,:), 'DisplayName', '$R_{z,\{K\}}/M_{z,\{K\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoK(1, 3), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-     'DisplayName', '$D_{x,\{K\}}/M_{z,\{K\}}$');
-plot(freqs, abs(squeeze(freqresp(G_CoK(3, 1), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-     'DisplayName', '$R_{z,\{K\}}/F_{x,\{K\}}$');
-hold off;
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Kagnitude');
-ylim([1e-10, 1e-3]);
-leg = legend('location', 'southeast', 'FontSize', 8, 'NumColumns', 2);
-leg.ItemTokenSize(1) = 18;
-
-%% Modal decoupling
-% Compute the eigen vectors
-[phi, wi] = eig(M\K);
-% Sort the eigen vectors by increasing associated frequency
-[~, i] = sort(diag(wi));
-phi = phi(:, i);
-
-% Plant in the modal space
-Gm = inv(phi)*inv(J_CoM)*G_L*inv(J_CoM')*inv(phi');
-
-%% Modal decoupled plant
-figure;
-hold on;
-plot(freqs, abs(squeeze(freqresp(Gm(1,1), freqs, 'Hz'))), 'color', colors(1,:), 'DisplayName', '$\mathcal{X}_{m,1}/\tau_{m,1}$');
-plot(freqs, abs(squeeze(freqresp(Gm(2,2), freqs, 'Hz'))), 'color', colors(2,:), 'DisplayName', '$\mathcal{X}_{m,2}/\tau_{m,2}$');
-plot(freqs, abs(squeeze(freqresp(Gm(3,3), freqs, 'Hz'))), 'color', colors(3,:), 'DisplayName', '$\mathcal{X}_{m,3}/\tau_{m,3}$');
-hold off;
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-ylim([1e-8, 1e-4]);
-leg = legend('location', 'northeast', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;
-
-%% SVD Decoupling
-wc = 2*pi*100; % Decoupling frequency [rad/s]
-% System's response at the decoupling frequency
-H1 = evalfr(G_L, j*wc);
-
-% Real approximation of G(j.wc)
-D = pinv(real(H1'*H1));
-H1 = pinv(D*real(H1'*diag(exp(j*angle(diag(H1*D*H1.'))/2))));
-
-[U,S,V] = svd(H1);
-
-Gsvd = inv(U)*G_L*inv(V');
-
-figure;
-hold on;
-for i_in = 1:3
-    for i_out = [i_in+1:3]
-        plot(freqs, abs(squeeze(freqresp(Gsvd(i_out, i_in), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-             'HandleVisibility', 'off');
-    end
-end
-plot(freqs, abs(squeeze(freqresp(Gsvd(1, 2), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-     'DisplayName', '$G_{SVD}(i,j)\ i \neq j$');
-set(gca,'ColorOrderIndex',1)
-for i_in_out = 1:3
-    plot(freqs, abs(squeeze(freqresp(Gsvd(i_in_out, i_in_out), freqs, 'Hz'))), 'DisplayName', sprintf('$G_{SVD}(%d,%d)$', i_in_out, i_in_out));
-end
-hold off;
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-ylim([1e-10, 2e-4]);
-leg = legend('location', 'northeast', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;
-
-%% Simscape model with relative motion sensor at alternative positions
-mdl = 'detail_control_decoupling_test_model';
-open(mdl)
-
-deq = 0.2; % Length of the actuators [m]
-
-% Input/Output definition
-clear io; io_i = 1;
-io(io_i) = linio([mdl, '/F1'], 1, 'openinput');  io_i = io_i + 1;
-io(io_i) = linio([mdl, '/F2'], 1, 'openinput');  io_i = io_i + 1;
-io(io_i) = linio([mdl, '/F3'], 1, 'openinput');  io_i = io_i + 1;
-io(io_i) = linio([mdl, '/Payload'], 1, 'openoutput'); io_i = io_i + 1;
-io(io_i) = linio([mdl, '/Payload'], 2, 'openoutput'); io_i = io_i + 1;
-io(io_i) = linio([mdl, '/Payload'], 3, 'openoutput'); io_i = io_i + 1;
-
-G_L_alt = linearize(mdl, io);
-G_L_alt.InputName  = {'F1', 'F2', 'F3'};
-G_L_alt.OutputName = {'d1', 'd2', 'd32'};
-
-% SVD Decoupling with the new plant
-wc = 2*pi*100; % Decoupling frequency [rad/s]
-% System's response at the decoupling frequency
-H1 = evalfr(G_L_alt, j*wc);
-
-% Real approximation of G(j.wc)
-D = pinv(real(H1'*H1));
-H1 = pinv(D*real(H1'*diag(exp(j*angle(diag(H1*D*H1.'))/2))));
-
-[U,S,V] = svd(H1);
-
-Gsvd_alt = inv(U)*G_L_alt*inv(V');
-
-%% Obtained plant after SVD decoupling - Relative motion sensors are not collocated with the actuators
-figure;
-hold on;
-for i_in = 1:3
-    for i_out = [i_in+1:3]
-        plot(freqs, abs(squeeze(freqresp(Gsvd_alt(i_out, i_in), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-             'HandleVisibility', 'off');
-    end
-end
-plot(freqs, abs(squeeze(freqresp(Gsvd_alt(1, 2), freqs, 'Hz'))), 'color', [0,0,0,0.2], ...
-     'DisplayName', '$G_{SVD}(i,j)\ i \neq j$');
-set(gca,'ColorOrderIndex',1)
-for i_in_out = 1:3
-    plot(freqs, abs(squeeze(freqresp(Gsvd_alt(i_in_out, i_in_out), freqs, 'Hz'))), 'DisplayName', sprintf('$G_{SVD}(%d,%d)$', i_in_out, i_in_out));
-end
-hold off;
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-ylim([5e-11, 7e-5]);
-leg = legend('location', 'southwest', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;

matlab/detail_control_3_close_loop_shaping.m

@@ -1,238 +0,0 @@
-%% Clear Workspace and Close figures
-clear; close all; clc;
-
-%% Intialize Laplace variable
-s = zpk('s');
-
-%% Path for functions, data and scripts
-addpath('./src/'); % Path for functions
-
-%% Colors for the figures
-colors = colororder;
-
-%% Initialize Frequency Vector
-freqs = logspace(-1, 3, 1000);
-
-%% Analytical Complementary Filters - Effect of alpha
-freqs_study = logspace(-2, 2, 1000);
-alphas = [0.1, 1, 10];
-w0 = 2*pi*1;
-s = tf('s');
-
-figure;
-hold on;
-for i = 1:length(alphas)
-    alpha = alphas(i);
-    Hh2 = (s/w0)^2*((s/w0)+1+alpha)/(((s/w0)+1)*((s/w0)^2 + alpha*(s/w0) + 1));
-    Hl2 = ((1+alpha)*(s/w0)+1)/(((s/w0)+1)*((s/w0)^2 + alpha*(s/w0) + 1));
-    plot(freqs_study, abs(squeeze(freqresp(Hh2, freqs_study, 'Hz'))), 'color', colors(i,:), 'DisplayName', sprintf('$\\alpha = %g$', alphas(i)));
-    plot(freqs_study, abs(squeeze(freqresp(Hl2, freqs_study, 'Hz'))), 'color', colors(i,:), 'HandleVisibility', 'off');
-end
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Relative Frequency $\frac{\omega}{\omega_0}$'); ylabel('Magnitude');
-hold off;
-ylim([1e-3, 20]);
-leg = legend('location', 'northeast', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;
-
-%% Analytical Complementary Filters - Effect of w0
-freqs_study = logspace(-1, 3, 1000);
-alpha = [1];
-w0s = [2*pi*1, 2*pi*10, 2*pi*100];
-s = tf('s');
-
-figure;
-hold on;
-for i = 1:length(w0s)
-    w0 =w0s(i);
-    Hh2 = (s/w0)^2*((s/w0)+1+alpha)/(((s/w0)+1)*((s/w0)^2 + alpha*(s/w0) + 1));
-    Hl2 = ((1+alpha)*(s/w0)+1)/(((s/w0)+1)*((s/w0)^2 + alpha*(s/w0) + 1));
-    plot(freqs_study, abs(squeeze(freqresp(Hh2, freqs_study, 'Hz'))), 'color', colors(i,:), 'DisplayName', sprintf('$\\omega_0 = %g$ Hz', w0/2/pi));
-    plot(freqs_study, abs(squeeze(freqresp(Hl2, freqs_study, 'Hz'))), 'color', colors(i,:), 'HandleVisibility', 'off');
-end
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-hold off;
-xlim([freqs_study(1), freqs_study(end)]); ylim([1e-3, 20]);
-leg = legend('location', 'southeast', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;
-
-%% Test model
-freqs = logspace(0, 3, 1000); % Frequency Vector [Hz]
-
-m = 20;  % mass [kg]
-k = 1e6; % stiffness [N/m]
-c = 1e2; % damping [N/(m/s)]
-
-% Plant dynamics
-G = 1/(m*s^2 + c*s + k);
-
-% Uncertainty weight
-wI = generateWF('n', 2, 'w0', 2*pi*50, 'G0', 0.1, 'Ginf', 10, 'Gc', 1);
-
-%% Bode plot of the plant with dynamical uncertainty
-figure;
-tiledlayout(3, 1, 'TileSpacing', 'Compact', 'Padding', 'None');
-
-% Magnitude
-ax1 = nexttile([2,1]);
-hold on;
-plot(freqs, abs(squeeze(freqresp(G, freqs, 'Hz'))), 'k-', 'DisplayName', 'G');
-plotMagUncertainty(wI, freqs, 'G', G, 'DisplayName', '$\Pi_i$');
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-ylabel('Magnitude [m/N]'); set(gca, 'XTickLabel',[]);
-ylim([1e-8, 7e-5]);
-hold off;
-leg = legend('location', 'northeast', 'FontSize', 8);
-leg.ItemTokenSize(1) = 18;
-
-% Phase
-ax2 = nexttile;
-hold on;
-plotPhaseUncertainty(wI, freqs, 'G', G);
-plot(freqs, 180/pi*unwrap(angle(squeeze(freqresp(G, freqs, 'Hz')))), 'k-');
-set(gca,'xscale','log');
-yticks(-360:90:90);
-ylim([-270 45]);
-xlabel('Frequency [Hz]'); ylabel('Phase [deg]');
-hold off;
-
-linkaxes([ax1,ax2],'x');
-xlim([freqs(1), freqs(end)]);
-
-%% Analytical Complementary Filters
-w0 = 2*pi*20;
-alpha = 1;
-
-Hh = (s/w0)^2*((s/w0)+1+alpha)/(((s/w0)+1)*((s/w0)^2 + alpha*(s/w0) + 1));
-Hl = ((1+alpha)*(s/w0)+1)/(((s/w0)+1)*((s/w0)^2 + alpha*(s/w0) + 1));
-
-%% Specifications
-figure;
-hold on;
-plot([1, 100], [0.01, 100], ':', 'color', colors(2,:));
-plot([300, 1000], [0.01, 0.01], ':', 'color', colors(1,:));
-plot(freqs, 1./abs(squeeze(freqresp(wI, freqs, 'Hz'))), ':', 'color', colors(1,:));
-plot(freqs, abs(squeeze(freqresp(Hl, freqs, 'Hz'))), '-', 'color', colors(1,:));
-plot(freqs, abs(squeeze(freqresp(Hh, freqs, 'Hz'))), '-', 'color', colors(2,:));
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-hold off;
-xlim([freqs(1), freqs(end)]);
-ylim([1e-3, 10]);
-xticks([0.1, 1, 10, 100, 1000]);
-
-%% Obtained controller
-omega = 2*pi*1000;
-
-K = 1/(Hh*G) * 1/((1+s/omega+(s/omega)^2));
-K = zpk(minreal(K));
-
-%% Bode plot of the controller K
-figure;
-tiledlayout(3, 1, 'TileSpacing', 'Compact', 'Padding', 'None');
-
-% Magnitude
-ax1 = nexttile([2, 1]);
-plot(freqs, abs(squeeze(freqresp(K*Hl, freqs, 'Hz'))), 'k-');
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-ylabel('Magnitude'); set(gca, 'XTickLabel',[]);
-ylim([8e3, 1e8])
-
-% Phase
-ax2 = nexttile;
-plot(freqs, 180/pi*angle(squeeze(freqresp(K*Hl, freqs, 'Hz'))), 'k-');
-set(gca,'xscale','log');
-yticks(-180:45:180);
-ylim([-180 45]);
-xlabel('Frequency [Hz]'); ylabel('Phase [deg]');
-
-linkaxes([ax1,ax2],'x');
-xlim([freqs(1), freqs(end)]);
-
-num_delta_points = 50;
-theta = linspace(0, 2*pi, num_delta_points);
-delta_points = exp(1j * theta);
-
-% Get frequency responses for all components
-G_resp  = squeeze(freqresp(G,  freqs, 'Hz'));
-K_resp  = squeeze(freqresp(K,  freqs, 'Hz'));
-Hl_resp = squeeze(freqresp(Hl, freqs, 'Hz'));
-wI_resp = squeeze(freqresp(wI, freqs, 'Hz'));
-
-% Calculate nominal responses
-nom_L = G_resp .* K_resp .* Hl_resp;
-nom_S = 1 ./ (1 + nom_L);
-nom_T = nom_L ./ (1 + nom_L);
-
-% Store all the points in the complex plane that L can take
-loop_region_points = zeros(length(freqs), num_delta_points);
-
-% Initialize arrays to store magnitude bounds
-S_mag_min = ones(length(freqs), 1) * inf;
-S_mag_max = zeros(length(freqs), 1);
-T_mag_min = ones(length(freqs), 1) * inf;
-T_mag_max = zeros(length(freqs), 1);
-
-% Calculate magnitude bounds for all delta values
-for i = 1:num_delta_points
-    % Perturbed loop gain
-    loop_perturbed = nom_L .* (1 + wI_resp .* delta_points(i));
-    loop_region_points(:,i) = loop_perturbed;
-
-    % Perturbed sensitivity function
-    S_perturbed = 1 ./ (1 + loop_perturbed);
-    S_mag = abs(S_perturbed);
-
-    % Update S magnitude bounds
-    S_mag_min = min(S_mag_min, S_mag);
-    S_mag_max = max(S_mag_max, S_mag);
-
-    % Perturbed complementary sensitivity function
-    T_perturbed = loop_perturbed ./ (1 + loop_perturbed);
-    T_mag = abs(T_perturbed);
-
-    % Update T magnitude bounds
-    T_mag_min = min(T_mag_min, T_mag);
-    T_mag_max = max(T_mag_max, T_mag);
-end
-
-% At frequencies where |wI| > 1, T min is zero
-T_mag_min(abs(wI_resp)>1) = 1e-10;
-
-%% Nyquist plot to check Robust Stability
-figure;
-hold on;
-plot(real(squeeze(freqresp(G*K*Hl, freqs, 'Hz'))), imag(squeeze(freqresp(G*K*Hl, freqs, 'Hz'))), 'k', 'DisplayName', '$L(j\omega)$ - Nominal');
-plot(alphaShape(real(loop_region_points(:)), imag(loop_region_points(:)), 0.1), 'FaceColor', [0, 0, 0], 'EdgeColor', 'none', 'FaceAlpha', 0.3, 'DisplayName', '$L(j\omega)$ - $\forall G \in \Pi_i$');
-plot(-1, 0, 'k+', 'MarkerSize', 5, 'HandleVisibility', 'off');
-hold off;
-grid on;
-axis equal
-xlim([-1.4, 0.2]); ylim([-1.2, 0.4]);
-xticks(-1.4:0.2:0.2); yticks(-1.2:0.2:0.4);
-xlabel('Real Part'); ylabel('Imaginary Part');
-leg = legend('location', 'southeast', 'FontSize', 8, 'NumColumns', 1);
-leg.ItemTokenSize(1) = 18;
-
-%% Robust Performance
-figure;
-hold on;
-plot(freqs, abs(nom_S), 'color', colors(2,:), 'DisplayName', '$|S|$ - Nom.');
-plot(freqs, abs(nom_T), 'color', colors(1,:), 'DisplayName', '$|T|$ - Nom.');
-
-patch([freqs, fliplr(freqs)], [S_mag_max', fliplr(S_mag_min')], colors(2,:), 'FaceAlpha', 0.2, 'EdgeColor', 'none', 'HandleVisibility', 'off');
-patch([freqs, fliplr(freqs)], [T_mag_max', fliplr(T_mag_min')], colors(1,:), 'FaceAlpha', 0.2, 'EdgeColor', 'none', 'HandleVisibility', 'off');
-
-plot([1, 100], [0.01, 100], ':', 'color', colors(2,:), 'DisplayName', 'Specs.');
-plot([300, 1000], [0.01, 0.01], ':', 'color', colors(1,:), 'DisplayName', 'Specs.');
-plot(freqs, 1./abs(squeeze(freqresp(wI, freqs, 'Hz'))), ':', 'color', colors(1,:), 'HandleVisibility', 'off');
-
-set(gca, 'XScale', 'log'); set(gca, 'YScale', 'log');
-hold off;
-xlabel('Frequency [Hz]'); ylabel('Magnitude');
-xlim([freqs(1), freqs(end)]);
-ylim([1e-4, 5]);
-xticks([0.1, 1, 10, 100, 1000]);
-leg = legend('location', 'southwest', 'FontSize', 8, 'NumColumns', 3);
-leg.ItemTokenSize(1) = 18;

nass-control.org

@@ -862,66 +862,6 @@ Input usage due to reference signal $r$ is determined by $\big|\frac{u}{r}\big|
 
 Proper choice of $|K_r|$ is then useful to limit input usage due to change of reference signal.
 
-*** Tikz Figures
-
-#+begin_src latex :file detail_control_decoupling_control_struts.pdf
-\begin{tikzpicture}
-  \node[block] (Gl) {$\bm{G}_{\{\mathcal{L}\}}$};
-
-  % Connections and labels
-  \draw[<-] (Gl.west) -- ++(-0.8, 0) node[above right]{$\bm{\tau}$};
-  \draw[->] (Gl.east) -- ++( 0.8, 0) node[above left]{$\bm{\mathcal{L}}$};
-\end{tikzpicture}
-#+end_src
-
-#+RESULTS:
-[[file:figs/detail_control_decoupling_control_struts.png]]
-
-
-#+begin_src latex :file detail_control_decoupling_control_jacobian_CoM.pdf
-\begin{tikzpicture}
-  \node[block] (G) {$\bm{G}_{\{\mathcal{L}\}}$};
-  \node[block, left=0.6 of G] (Jt) {$\bm{J}_{\{M\}}^{-\intercal}$};
-  \node[block, right=0.6 of G] (Ja) {$\bm{J}_{\{M\}}^{-1}$};
-
-  % Connections and labels
-  \draw[<-] (Jt.west) -- ++(-1.4, 0) node[above right]{$\bm{\mathcal{F}}_{\{M\}}$};
-  \draw[->] (Jt.east) -- (G.west)  node[above left]{$\bm{\tau}$};
-  \draw[->] (G.east) -- (Ja.west)  node[above left]{$\bm{\mathcal{L}}$};
-  \draw[->] (Ja.east) -- ++( 1.4, 0)  node[above left]{$\bm{\mathcal{X}}_{\{M\}}$};
-
-  \begin{scope}[on background layer]
-    \node[fit={(Jt.south west) (Ja.north east)}, fill=black!10!white, draw, dashed, inner sep=4pt] (Gx) {};
-    \node[above] at (Gx.north) {$\bm{G}_{\{M\}}$};
-  \end{scope}
-\end{tikzpicture}
-#+end_src
-
-#+RESULTS:
-[[file:figs/detail_control_decoupling_control_jacobian_CoM.png]]
-
-#+begin_src latex :file detail_control_decoupling_control_jacobian_CoK.pdf
-\begin{tikzpicture}
-  \node[block] (G) {$\bm{G}_{\{\mathcal{L}\}}$};
-  \node[block, left=0.6 of G] (Jt) {$\bm{J}_{\{K\}}^{-\intercal}$};
-  \node[block, right=0.6 of G] (Ja) {$\bm{J}_{\{K\}}^{-1}$};
-
-  % Connections and labels
-  \draw[<-] (Jt.west) -- ++(-1.4, 0) node[above right]{$\bm{\mathcal{F}}_{\{K\}}$};
-  \draw[->] (Jt.east) -- (G.west)  node[above left]{$\bm{\tau}$};
-  \draw[->] (G.east) -- (Ja.west)  node[above left]{$\bm{\mathcal{L}}$};
-  \draw[->] (Ja.east) -- ++( 1.4, 0)  node[above left]{$\bm{\mathcal{X}}_{\{K\}}$};
-
-  \begin{scope}[on background layer]
-    \node[fit={(Jt.south west) (Ja.north east)}, fill=black!10!white, draw, dashed, inner sep=4pt] (Gx) {};
-    \node[above] at (Gx.north) {$\bm{G}_{\{K\}}$};
-  \end{scope}
-\end{tikzpicture}
-#+end_src
-
-#+RESULTS:
-[[file:figs/detail_control_decoupling_control_jacobian_CoK.png]]
-
 ** DONE [#A] Fix the outline
 CLOSED: [2025-04-03 Thu 12:01]
 
@@ -999,41 +939,32 @@ Prefixes:
 ** DONE [#A] Finish writing "multiple sensor" control section
 CLOSED: [2025-04-09 Wed 13:55] SCHEDULED: <2025-04-08 Tue>
 
-** TODO [#A] Rework table that compares decoupling strategies
-SCHEDULED: <2025-04-13 Sun>
-
 ** TODO [#B] Review of control for Stewart platforms?
 
 [[file:~/Cloud/work-projects/ID31-NASS/matlab/stewart-simscape/org/bibliography.org::*Control][Control]]
 
 Or html version: https://research.tdehaeze.xyz/stewart-simscape/docs/bibliography.html
 
-** CANC [#C] Discuss different strategies?
+** TODO [#C] Discuss different strategies?
-CLOSED: [2025-04-13 Sun 10:40]
 
-- State "CANC"       from "TODO"       [2025-04-13 Sun 10:40]
 - Robust control
 - Adaptive control
 - etc...
 
 * Introduction                                                        :ignore:
 
-Three critical elements for the control of parallel manipulators such as the Nano-Hexapod were identified: effective utilization and combination of multiple sensors, appropriate plant decoupling strategies, and robust controller design for the decoupled system.
+When controlling a MIMO system (specifically parallel manipulator such as the Stewart platform?)
 
-During the conceptual design phase of the NASS, pragmatic approaches were implemented for each of these elements.
+- [ ] *Should the quick review of Stewart platform control be here?*
-The High Authority Control-Low Authority Control (HAC-LAC) architecture was selected for combining sensors.
+  In that case it should be possible to highlight three areas:
-Control was implemented in the frame of the struts, leveraging the inherent low-frequency decoupling of the plant where all decoupled elements exhibited similar dynamics, thereby simplifying the Single-Input Single-Output (SISO) controller design process.
+  - use of multiple sensors
-For these decoupled plants, open-loop shaping techniques were employed to tune the individual controllers.
+  - decoupling strategy
+  - control optimization
 
-While these initial strategies proved effective in validating the NASS concept, this work explores alternative approaches with the potential to further enhance the performance.
+Several considerations:
-Section ref:sec:detail_control_sensor examines different methods for combining multiple sensors, with particular emphasis on sensor fusion techniques that utilize complementary filters.
+- Section ref:sec:detail_control_sensor: How to most effectively use/combine multiple sensors
-A novel approach for designing these filters is proposed, which allows optimization of the sensor fusion effectiveness.
+- Section ref:sec:detail_control_decoupling: How to decouple a system
-
+- Section ref:sec:detail_control_cf: How to design the controller
-Section ref:sec:detail_control_decoupling presents a comparative analysis of various decoupling strategies, including Jacobian decoupling, modal decoupling, and Singular Value Decomposition (SVD) decoupling.
-Each method is evaluated in terms of its theoretical foundations, implementation requirements, and performance characteristics, providing insights into their respective advantages for different applications.
-
-Finally, Section ref:sec:detail_control_cf addresses the challenge of controller design for decoupled plants.
-A method for directly shaping closed-loop transfer functions using complementary filters is proposed, offering an intuitive approach to achieving desired performance specifications while ensuring robustness to plant uncertainty.
 
 * Multiple Sensor Control
 :PROPERTIES:
@@ -1044,9 +975,10 @@ A method for directly shaping closed-loop transfer functions using complementary
 ** Introduction                                                      :ignore:
 
 The literature review of Stewart platforms revealed a wide diversity of designs with various sensor and actuator configurations.
-Control objectives (such as active damping, vibration isolation, or precise positioning) directly dictate sensor selection, whether inertial, force, or relative position sensors.
+Control objectives (such as active damping, vibration isolation, or precise positioning) dictate specific sensor configurations.
+The selection between inertial sensors, force sensors, or relative position sensors is primarily determined by the system's control requirements.
 
-In cases where multiple control objectives must be achieved simultaneously, as is the case for the Nano Active Stabilization System (NASS) where the Stewart platform must both position the sample and provide isolation from micro-station vibrations, combining multiple sensors within the control architecture has been demonstrated to yield significant performance benefits [[cite:&hauge04_sensor_contr_space_based_six]].
+In cases where multiple control objectives must be achieved simultaneously, as is the case for the Nano Active Stabilization System (NASS) where the Stewart platform must both position the sample and provide isolation from micro-station vibrations, combining multiple sensors within the control architecture has been demonstrated to yield significant performance benefits.
 From the literature, three principal approaches for combining sensors have been identified: High Authority Control-Low Authority Control (HAC-LAC), sensor fusion, and two-sensor control architectures.
 
 #+begin_src latex :file detail_control_sensor_arch_hac_lac.pdf
@@ -1171,7 +1103,7 @@ From the literature, three principal approaches for combining sensors have been
 #+end_subfigure
 #+end_figure
 
-The HAC-LAC approach employs a dual-loop control strategy in which two control loops utilize different sensors for distinct purposes (Figure ref:fig:detail_control_sensor_arch_hac_lac).
+The HAC-LAC approach, implemented during the conceptual phase, employs a dual-loop control strategy in which two control loops utilize different sensors for distinct purposes (Figure ref:fig:detail_control_sensor_arch_hac_lac).
 In [[cite:&li01_simul_vibrat_isolat_point_contr]], vibration isolation is provided by accelerometers collocated with the voice coil actuators, while external rotational sensors are utilized to achieve pointing control.
 In [[cite:&geng95_intel_contr_system_multip_degree]], force sensors collocated with the magnetostrictive actuators are used for active damping using decentralized IFF, and subsequently accelerometers are employed for adaptive vibration isolation.
 Similarly, in [[cite:&wang16_inves_activ_vibrat_isolat_stewar]], piezoelectric actuators with collocated force sensors are used in a decentralized manner to provide active damping while accelerometers are implemented in an adaptive feedback loop to suppress periodic vibrations.
@@ -1179,7 +1111,7 @@ In [[cite:&xie17_model_contr_hybrid_passiv_activ]], force sensors are integrated
 
 The second approach, sensor fusion (illustrated in Figure ref:fig:detail_control_sensor_arch_sensor_fusion), involves filtering signals from two sensors using complementary filters[fn:detail_control_1] and summing them to create an improved sensor signal.
 In [[cite:&hauge04_sensor_contr_space_based_six]], geophones (used at low frequency) are merged with force sensors (used at high frequency).
-It is demonstrated that combining both sensors using sensor fusion can improve performance compared to using only one of the two sensors.
+It is demonstrated that combining both sensors using sensor fusion can improve performance compared to using the individual sensors independently.
 In [[cite:&tjepkema12_sensor_fusion_activ_vibrat_isolat_precis_equip]], sensor fusion architecture is implemented with an accelerometer and a force sensor.
 This implementation is shown to simultaneously achieve high damping of structural modes (through the force sensors) while maintaining very low vibration transmissibility (through the accelerometers).
 
@@ -1192,21 +1124,26 @@ A "two-sensor control" approach was proven to perform better than controllers ba
 A Linear Quadratic Regulator (LQG) was employed to optimize the two-input/one-output controller.
 
 Beyond these three main approaches, other control architectures have been proposed for different purposes.
-For instance, in [[cite:&yang19_dynam_model_decoup_contr_flexib]], a first control loop utilizes force sensors and relative motion sensors to compensate for parasitic stiffness of the flexible joints.
+In [[cite:&yang19_dynam_model_decoup_contr_flexib]], a first control loop utilizes force sensors and relative motion sensors to compensate for parasitic stiffness of the flexible joints.
 Subsequently, the system is decoupled in the modal space (facilitated by the removal of parasitic stiffness) and accelerometers are employed for vibration isolation.
 
 The HAC-LAC architecture was previously investigated during the conceptual phase and successfully implemented to validate the NASS concept, demonstrating excellent performance.
 At the other end of the spectrum, the two-sensor approach yields greater control design freedom but introduces increased complexity in tuning, and thus was not pursued in this study.
 This work instead focuses on sensor fusion, which represents a promising middle ground between the proven HAC-LAC approach and the more complex two-sensor control strategy.
 
-A review of sensor fusion is first presented in Section ref:ssec:detail_control_sensor_review.
+A review of sensor fusion is first presented (Section ref:ssec:detail_control_sensor_review), followed by an examination of the fundamental theoretical concepts (Section ref:ssec:detail_control_sensor_fusion_requirements).
-Then, in Section ref:ssec:detail_control_sensor_fusion_requirements, both the robustness of the fusion and the noise characteristics of the resulting "fused sensor" are derived and expressed as functions of the complementary filters' norms.
+In this section, both the robustness of the fusion and the noise characteristics of the resulting "super sensor" are derived and expressed as functions of the complementary filters' norms.
-A synthesis method for shaping complementary filters is proposed in Section ref:ssec:detail_control_sensor_hinf_method.
+A synthesis method for designing complementary filters that allow to shape their norms is proposed (Section ref:ssec:detail_control_sensor_hinf_method).
 The investigation is then extended beyond the conventional two-sensor scenario, demonstrating how the proposed complementary filter synthesis can be generalized for applications requiring the fusion of three or more sensors (Section ref:ssec:detail_control_sensor_hinf_three_comp_filters).
 
 ** Review of Sensor Fusion
 <<ssec:detail_control_sensor_review>>
 
+Sensors used to measure physical quantities have two primary limitations: measurement accuracy which is compromised by various noise sources (including electrical noise from conditioning electronics), and limited measurement bandwidth.
+Sensor fusion offers a solution to these limitations by combining multiple sensors [[cite:&bendat57_optim_filter_indep_measur_two]].
+By strategically selecting sensors with complementary characteristics, a "super sensor" can be created that combines the advantages of each individual sensor.
+
+
 Measuring a physical quantity using sensors is always subject to several limitations.
 First, the accuracy of the measurement is affected by various noise sources, such as electrical noise from the conditioning electronics.
 Second, the frequency range in which the measurement is relevant is bounded by the bandwidth of the sensor.
@@ -1220,7 +1157,7 @@ In other applications, sensor fusion is utilized to obtain an estimate of the me
 More recently, the fusion of sensors measuring different physical quantities has been proposed to enhance control properties [[cite:&collette15_sensor_fusion_method_high_perfor;&yong16_high_speed_vertic_posit_stage]].
 In [[cite:&collette15_sensor_fusion_method_high_perfor]], an inertial sensor used for active vibration isolation is fused with a sensor collocated with the actuator to improve the stability margins of the feedback controller.
 
-Beyond Stewart platforms, practical applications of sensor fusion are numerous.
+On top of Stewart platforms, practical applications of sensor fusion are numerous.
 It is widely implemented for attitude estimation in autonomous vehicles such as unmanned aerial vehicles [[cite:&baerveldt97_low_cost_low_weigh_attit;&corke04_inert_visual_sensin_system_small_auton_helic;&jensen13_basic_uas]] and underwater vehicles [[cite:&pascoal99_navig_system_desig_using_time;&batista10_optim_posit_veloc_navig_filter_auton_vehic]].
 Sensor fusion offers significant benefits for high-performance positioning control as demonstrated in [[cite:&shaw90_bandw_enhan_posit_measur_using_measur_accel;&zimmermann92_high_bandw_orien_measur_contr;&min15_compl_filter_desig_angle_estim;&yong16_high_speed_vertic_posit_stage]].
 It has also been identified as a key technology for improving the performance of active vibration isolation systems [[cite:&tjepkema12_sensor_fusion_activ_vibrat_isolat_precis_equip]].
@@ -1236,10 +1173,14 @@ In early implementations of complementary filtering, analog circuits were used t
 While analog complementary filters remain in use today [[cite:&yong16_high_speed_vertic_posit_stage;&moore19_capac_instr_sensor_fusion_high_bandw_nanop]], digital implementation is now more common as it provides greater flexibility.
 
 Various design methods have been developed to optimize complementary filters.
-The most straightforward approach utilizes analytical formulas, which depending on the application may be first order [[cite:&corke04_inert_visual_sensin_system_small_auton_helic;&yeh05_model_contr_hydraul_actuat_two;&yong16_high_speed_vertic_posit_stage]], second order [[cite:&baerveldt97_low_cost_low_weigh_attit;&stoten01_fusion_kinet_data_using_compos_filter;&jensen13_basic_uas]], or higher orders [[cite:&shaw90_bandw_enhan_posit_measur_using_measur_accel;&zimmermann92_high_bandw_orien_measur_contr;&stoten01_fusion_kinet_data_using_compos_filter;&collette15_sensor_fusion_method_high_perfor;&matichard15_seism_isolat_advan_ligo]].
+The most straightforward approach utilizes analytical formulas.
-Since the characteristics of the super sensor depend on proper complementary filter design [[cite:&dehaeze19_compl_filter_shapin_using_synth]], several optimization techniques have emerged—ranging from optimizing parameters for analytical formulas [[cite:&jensen13_basic_uas;&min15_compl_filter_desig_angle_estim;&fonseca15_compl]] to employing convex optimization tools [[cite:&hua04_polyp_fir_compl_filter_contr_system;&hua05_low_ligo]] such as linear matrix inequalities [[cite:&pascoal99_navig_system_desig_using_time]].
+Depending on the application, these formulas may be of first order [[cite:&corke04_inert_visual_sensin_system_small_auton_helic;&yeh05_model_contr_hydraul_actuat_two;&yong16_high_speed_vertic_posit_stage]], second order [[cite:&baerveldt97_low_cost_low_weigh_attit;&stoten01_fusion_kinet_data_using_compos_filter;&jensen13_basic_uas]], or higher orders [[cite:&shaw90_bandw_enhan_posit_measur_using_measur_accel;&zimmermann92_high_bandw_orien_measur_contr;&stoten01_fusion_kinet_data_using_compos_filter;&collette15_sensor_fusion_method_high_perfor;&matichard15_seism_isolat_advan_ligo]].
-As demonstrated in [[cite:&plummer06_optim_compl_filter_their_applic_motion_measur]], complementary filter design can be linked to the standard mixed-sensitivity control problem, allowing powerful classical control theory tools to be applied.
+
-For example, in [[cite:&jensen13_basic_uas]], two gains of a Proportional Integral (PI) controller are optimized to minimize super sensor noise.
+Since the characteristics of the super sensor depend on the proper design of complementary filters [[cite:&dehaeze19_compl_filter_shapin_using_synth]], several optimization techniques have been developed.
+Some approaches focus on finding optimal parameters for analytical formulas [[cite:&jensen13_basic_uas;&min15_compl_filter_desig_angle_estim;&fonseca15_compl]], while others employ convex optimization tools [[cite:&hua04_polyp_fir_compl_filter_contr_system;&hua05_low_ligo]] such as linear matrix inequalities [[cite:&pascoal99_navig_system_desig_using_time]].
+As demonstrated in [[cite:&plummer06_optim_compl_filter_their_applic_motion_measur]], complementary filter design can be linked to the standard mixed-sensitivity control problem.
+Consequently, the powerful tools developed for classical control theory can be applied to complementary filter design.
+For example, in [[cite:&jensen13_basic_uas]], the two gains of a Proportional Integral (PI) controller are optimized to minimize super sensor noise.
 
 All these complementary filter design methods share the common objective of creating a super sensor with desired characteristics, typically in terms of noise and dynamics.
 As reported in [[cite:&zimmermann92_high_bandw_orien_measur_contr;&plummer06_optim_compl_filter_their_applic_motion_measur]], phase shifts and magnitude bumps in the super sensor dynamics may occur if complementary filters are poorly designed or if sensors are improperly calibrated.
@@ -1247,7 +1188,7 @@ Therefore, the robustness of the fusion must be considered when designing comple
 Despite the numerous design methods proposed in the literature, a simple approach that specifies desired super sensor characteristics while ensuring good fusion robustness has been lacking.
 
 Fortunately, both fusion robustness and super sensor characteristics can be linked to complementary filter magnitude [[cite:&dehaeze19_compl_filter_shapin_using_synth]].
-Based on this relationship, the present work introduces an approach to designing complementary filters using $\mathcal{H}_\infty\text{-synthesis}$, which enables intuitive shaping of complementary filter magnitude in a straightforward manner.
+Based on this relationship, the present work introduces an approach to designing complementary filters using $\mathcal{H}_\infty$ synthesis, which enables intuitive shaping of complementary filter magnitude in a straightforward manner.
 
 ** Matlab Init                                              :noexport:ignore:
 #+begin_src matlab :tangle no :exports none :results silent :noweb yes :var current_dir=(file-name-directory buffer-file-name)
@@ -1477,7 +1418,7 @@ The effects of imperfect normalization will be addressed subsequently.
 In that case, the super sensor output $\hat{x}$ equals $x$ plus the filtered noise from both sensors eqref:eq:detail_control_sensor_estimate_perfect_dyn.
 From this equation, it is evident that the complementary filters $H_1(s)$ and $H_2(s)$ operate solely on the sensor noise.
 Thus, this sensor fusion architecture allows filtering of sensor noise without introducing distortion in the measured physical quantity.
-This fundamental property necessitates that the two filters are complementary.
+This fundamental property necessitates that the two filters must be complementary.
 
 \begin{equation}\label{eq:detail_control_sensor_estimate_perfect_dyn}
   \hat{x} = x + H_1(s) n_1 + H_2(s) n_2
@@ -1499,14 +1440,16 @@ If the two sensors have identical noise characteristics ($\Phi_{n_1}(\omega) = \
 This represents the simplest form of sensor fusion using complementary filters.
 
 However, sensors typically exhibit high noise levels in different frequency regions.
-In such cases, to reduce the noise of the super sensor, $|H_1(j\omega)|$ should be minimized when $\Phi_{n_1}(\omega)$ exceeds $\Phi_{n_2}(\omega)$, and $|H_2(j\omega)|$ should be minimized when $\Phi_{n_2}(\omega)$ exceeds $\Phi_{n_1}(\omega)$.
+In such cases, to reduce the noise of the super sensor, the norm $|H_1(j\omega)|$ should be minimized when $\Phi_{n_1}(\omega)$ exceeds $\Phi_{n_2}(\omega)$, and the norm $|H_2(j\omega)|$ should be minimized when $\Phi_{n_2}(\omega)$ exceeds $\Phi_{n_1}(\omega)$.
 Therefore, by appropriately shaping the norm of the complementary filters, the noise of the super sensor can be minimized.
 
 **** Sensor Fusion Robustness
 
 In practical systems, sensor normalization is rarely perfect, and condition eqref:eq:detail_control_sensor_perfect_dynamics is not fully satisfied.
+
 To analyze such imperfections, a multiplicative input uncertainty is incorporated into the sensor dynamics (Figure ref:fig:detail_control_sensor_model_uncertainty).
 The nominal model is the estimated model used for normalization $\hat{G}_i(s)$, $\Delta_i(s)$ is any stable transfer function satisfying $|\Delta_i(j\omega)| \le 1,\ \forall\omega$, and $w_i(s)$ is a weighting transfer function representing the magnitude of uncertainty.
+The weight $w_i(s)$ is selected such that the actual sensor dynamics $G_i(j\omega)$ remains within the uncertain region represented by a circle in the complex plane, centered on $1$ with a radius equal to $|w_i(j\omega)|$.
 
 Since the nominal sensor dynamics is taken as the normalized filter, the normalized sensor model can be further simplified as shown in Figure ref:fig:detail_control_sensor_model_uncertainty_simplified.
 
@@ -1579,7 +1522,7 @@ Since the nominal sensor dynamics is taken as the normalized filter, the normali
 #+attr_latex: :width 0.95\linewidth
 [[file:figs/detail_control_sensor_model_uncertainty.png]]
 #+end_subfigure
-#+attr_latex: :caption \subcaption{\label{fig:detail_control_sensor_model_uncertainty_simplified}Simplified normalized sensor model}
+#+attr_latex: :caption \subcaption{\label{fig:detail_control_sensor_model_uncertainty_simplified}Simplified sensor model}
 #+attr_latex: :options {0.38\textwidth}
 #+begin_subfigure
 #+attr_latex: :width 0.95\linewidth
@@ -1591,6 +1534,11 @@ The sensor fusion architecture incorporating sensor models with dynamical uncert
 The super sensor dynamics eqref:eq:detail_control_sensor_super_sensor_dyn_uncertainty is no longer unity but depends on the sensor dynamical uncertainty weights $w_i(s)$ and the complementary filters $H_i(s)$.
 The dynamical uncertainty of the super sensor can be graphically represented in the complex plane by a circle centered on $1$ with a radius equal to $|w_1(j\omega) H_1(j\omega)| + |w_2(j\omega) H_2(j\omega)|$ (Figure ref:fig:detail_control_sensor_uncertainty_set_super_sensor).
 
+
+The sensor fusion architecture with the sensor models including dynamical uncertainty is shown in Figure ref:fig:detail_control_sensor_fusion_dynamic_uncertainty.
+The super sensor dynamics eqref:eq:detail_control_sensor_super_sensor_dyn_uncertainty is no longer equal to $1$ and now depends on the sensor dynamical uncertainty weights $w_i(s)$ as well as on the complementary filters $H_i(s)$.
+The dynamical uncertainty of the super sensor can be graphically represented in the complex plane by a circle centered on $1$ with a radius equal to $|w_1(j\omega) H_1(j\omega)| + |w_2(j\omega) H_2(j\omega)|$ (Figure ref:fig:detail_control_sensor_uncertainty_set_super_sensor).
+
 \begin{equation}\label{eq:detail_control_sensor_super_sensor_dyn_uncertainty}
   \frac{\hat{x}}{x} = 1 + w_1(s) H_1(s) \Delta_1(s) + w_2(s) H_2(s) \Delta_2(s)
 \end{equation}
@@ -1718,7 +1666,7 @@ As it is generally desired to limit the dynamical uncertainty of the super senso
 As established in Section ref:ssec:detail_control_sensor_fusion_requirements, the super sensor's noise characteristics and robustness are directly dependent on the complementary filters' norm.
 A synthesis method enabling precise shaping of these norms would therefore offer substantial practical benefits.
 This section develops such an approach by formulating the design objective as a standard $\mathcal{H}_\infty$ optimization problem.
-The methodology for designing appropriate weighting functions (which specify desired complementary filter shape during synthesis) is examined in detail, and the efficacy of the proposed method is validated with a simple example.
+The methodology for designing appropriate weighting functions (which specify desired complementary filter shapes during synthesis) is examined in detail, and the efficacy of the proposed method is validated with a simple example.
 
 **** Synthesis Objective
 
@@ -1736,7 +1684,8 @@ Weighting transfer functions $W_1(s)$ and $W_2(s)$ are strategically selected to
 
 **** Shaping of Complementary Filters using $\mathcal{H}_\infty$ synthesis
 
-The synthesis objective can be expressed as a standard $\mathcal{H}_\infty$ optimization problem by considering the generalized plant $P(s)$ illustrated in Figure ref:fig:detail_control_sensor_h_infinity_robust_fusion_plant and mathematically described by eqref:eq:detail_control_sensor_generalized_plant.
+The synthesis objective can be readily expressed as a standard $\mathcal{H}_\infty$ optimization problem and solved using widely available computational tools.
+Consider the generalized plant $P(s)$ illustrated in Figure ref:fig:detail_control_sensor_h_infinity_robust_fusion_plant and mathematically described by eqref:eq:detail_control_sensor_generalized_plant.
 
 \begin{equation}\label{eq:detail_control_sensor_generalized_plant}
   \begin{bmatrix} z_1 \\ z_2 \\ v \end{bmatrix} = P(s) \begin{bmatrix} w\\u \end{bmatrix}; \quad P(s) = \begin{bmatrix}W_1(s) & -W_1(s) \\ 0 & \phantom{+}W_2(s) \\  1 & 0 \end{bmatrix}
@@ -1805,7 +1754,7 @@ The synthesis objective can be expressed as a standard $\mathcal{H}_\infty$ opti
 #+end_src
 
 #+name: fig:detail_control_sensor_h_infinity_robust_fusion
-#+caption: Architecture for the $\mathcal{H}_\infty\text{-synthesis}$ of complementary filters
+#+caption: Architecture for the $\mathcal{H}_\infty$ synthesis of complementary filters
 #+attr_latex: :options [htbp]
 #+begin_figure
 #+attr_latex: :caption \subcaption{\label{fig:detail_control_sensor_h_infinity_robust_fusion_plant}Generalized plant}
@@ -1822,13 +1771,13 @@ The synthesis objective can be expressed as a standard $\mathcal{H}_\infty$ opti
 #+end_subfigure
 #+end_figure
 
-Applying standard $\mathcal{H}_\infty\text{-synthesis}$ to the generalized plant $P(s)$ is equivalent to finding a stable filter $H_2(s)$ that, based on input $v$, generates an output signal $u$ such that the $\mathcal{H}_\infty$ norm of the system shown in Figure ref:fig:detail_control_sensor_h_infinity_robust_fusion_fb from $w$ to $[z_1, \ z_2]$ does not exceed unity, as expressed in eqref:eq:detail_control_sensor_hinf_syn_obj.
+Applying standard $\mathcal{H}_\infty$ synthesis to the generalized plant $P(s)$ is equivalent to finding a stable filter $H_2(s)$ that, based on input $v$, generates an output signal $u$ such that the $\mathcal{H}_\infty$ norm of the system shown in Figure ref:fig:detail_control_sensor_h_infinity_robust_fusion_fb from $w$ to $[z_1, \ z_2]$ does not exceed unity, as expressed in eqref:eq:detail_control_sensor_hinf_syn_obj.
 
 \begin{equation}\label{eq:detail_control_sensor_hinf_syn_obj}
   \left\|\begin{matrix} \left(1 - H_2(s)\right) W_1(s) \\ H_2(s) W_2(s) \end{matrix}\right\|_\infty \le 1
 \end{equation}
 
-By defining $H_1(s)$ as the complement of $H_2(s)$ eqref:eq:detail_control_sensor_definition_H1, the $\mathcal{H}_\infty\text{-synthesis}$ objective becomes equivalent to eqref:eq:detail_control_sensor_hinf_problem, ensuring that conditions eqref:eq:detail_control_sensor_hinf_cond_h1 and eqref:eq:detail_control_sensor_hinf_cond_h2 are satisfied.
+By defining $H_1(s)$ as the complement of $H_2(s)$ (eqref:eq:detail_control_sensor_definition_H1), the $\mathcal{H}_\infty$ synthesis objective becomes equivalent to eqref:eq:detail_control_sensor_hinf_problem, ensuring that conditions eqref:eq:detail_control_sensor_hinf_cond_h1 and eqref:eq:detail_control_sensor_hinf_cond_h2 are satisfied.
 
 \begin{equation}\label{eq:detail_control_sensor_definition_H1}
   H_1(s) \triangleq 1 - H_2(s)
@@ -1838,20 +1787,20 @@ By defining $H_1(s)$ as the complement of $H_2(s)$ eqref:eq:detail_control_senso
   \left\|\begin{matrix} H_1(s) W_1(s) \\ H_2(s) W_2(s) \end{matrix}\right\|_\infty \le 1
 \end{equation}
 
-Therefore, applying $\mathcal{H}_\infty\text{-synthesis}$ to the standard plant $P(s)$ generates two filters, $H_2(s)$ and $H_1(s) \triangleq 1 - H_2(s)$, that are complementary as required by eqref:eq:detail_control_sensor_comp_filter_problem_form, with norms bounded by the specified constraints in eqref:eq:detail_control_sensor_hinf_cond_h1 and eqref:eq:detail_control_sensor_hinf_cond_h2.
+Therefore, applying $\mathcal{H}_\infty$ synthesis to the standard plant $P(s)$ (eqref:eq:detail_control_sensor_generalized_plant) generates two filters, $H_2(s)$ and $H_1(s) \triangleq 1 - H_2(s)$, that are complementary as required by eqref:eq:detail_control_sensor_comp_filter_problem_form, with norms bounded by the specified constraints in eqref:eq:detail_control_sensor_hinf_cond_h1 and eqref:eq:detail_control_sensor_hinf_cond_h2.
 
 It should be noted that there exists only an implication (not an equivalence) between the $\mathcal{H}_\infty$ norm condition in eqref:eq:detail_control_sensor_hinf_problem and the initial synthesis objectives in eqref:eq:detail_control_sensor_hinf_cond_h1 and eqref:eq:detail_control_sensor_hinf_cond_h2.
-Consequently, the optimization may be somewhat conservative with respect to the set of filters on which it operates [[cite:&skogestad07_multiv_feedb_contr,Chap. 2.8.3]].
+Consequently, the optimization may be somewhat conservative with respect to the set of filters on which it operates (see [[cite:&skogestad07_multiv_feedb_contr,Chap. 2.8.3]]).
 
 **** Weighting Functions Design
 
 Weighting functions play a crucial role during synthesis by specifying the maximum allowable norms for the complementary filters.
-The proper design of these weighting functions is essential for the successful implementation of the proposed $\mathcal{H}_\infty\text{-synthesis}$ approach.
+The proper design of these weighting functions is essential for the successful implementation of the proposed $\mathcal{H}_\infty$ synthesis approach.
 
 Three key considerations should guide the design of weighting functions.
 First, only proper and stable transfer functions should be employed.
 Second, the order of the weighting functions should remain reasonably small to minimize computational costs associated with solving the optimization problem and to facilitate practical implementation of the filters (as the order of the synthesized filters equals the sum of the weighting functions' orders).
-Third, the fundamental limitations imposed by the complementary property eqref:eq:detail_control_sensor_comp_filter must be respected, which implies that $|H_1(j\omega)|$ and $|H_2(j\omega)|$ cannot both be made small at the same frequency.
+Third, the fundamental limitations imposed by the complementary property (eqref:eq:detail_control_sensor_comp_filter) must be respected, which implies that $|H_1(j\omega)|$ and $|H_2(j\omega)|$ cannot both be made small at the same frequency.
 
 When designing complementary filters, it is typically desirable to specify their slopes, "blending" frequency, and maximum gains at low and high frequencies.
 To facilitate the expression of these specifications, formula eqref:eq:detail_control_sensor_weight_formula is proposed for the design of weighting functions.
@@ -1999,7 +1948,7 @@ exportFig('figs/detail_control_sensor_hinf_filters_results.pdf', 'width', 'half'
 [[file:figs/detail_control_sensor_hinf_filters_results.png]]
 #+end_minipage
 
-Standard $\mathcal{H}_\infty\text{-synthesis}$ is then applied to the generalized plant shown in Figure ref:fig:detail_control_sensor_h_infinity_robust_fusion_plant.
+Standard $\mathcal{H}_\infty$ synthesis is then applied to the generalized plant shown in Figure ref:fig:detail_control_sensor_h_infinity_robust_fusion_plant.
 This yields the filter $H_2(s)$ that minimizes the $\mathcal{H}_\infty$ norm from input $w$ to outputs $[z_1,\ z_2]^{\intercal}$.
 The resulting $\mathcal{H}_\infty$ norm is found to be close to unity, indicating successful synthesis: the norms of the complementary filters remain below the specified upper bounds.
 This is confirmed by the Bode plots of the obtained complementary filters in Figure ref:fig:detail_control_sensor_hinf_filters_results.
@@ -2125,7 +2074,7 @@ The synthesis objective is to compute a set of $n$ stable transfer functions $[H
 The transfer functions $[W_1(s),\ W_2(s),\ \dots,\ W_n(s)]$ are weights selected to specify the maximum complementary filters' norm during synthesis.
 
 This synthesis objective is closely related to the one described in Section ref:ssec:detail_control_sensor_hinf_method, and the proposed synthesis method represents a generalization of the approach previously presented.
-A set of $n$ complementary filters can be shaped by applying standard $\mathcal{H}_\infty\text{-synthesis}$ to the generalized plant $P_n(s)$ described by eqref:eq:detail_control_sensor_generalized_plant_n_filters.
+A set of $n$ complementary filters can be shaped by applying standard $\mathcal{H}_\infty$ synthesis to the generalized plant $P_n(s)$ described by eqref:eq:detail_control_sensor_generalized_plant_n_filters.
 
 \begin{equation}\label{eq:detail_control_sensor_generalized_plant_n_filters}
   \begin{bmatrix} z_1 \\ \vdots \\ z_n \\ v \end{bmatrix} = P_n(s) \begin{bmatrix} w \\ u_1 \\ \vdots \\ u_{n-1} \end{bmatrix}; \quad
@@ -2247,13 +2196,13 @@ Consider the generalized plant $P_3(s)$ shown in Figure ref:fig:detail_control_s
 #+end_src
 
 #+name: fig:detail_control_sensor_comp_filter_three_hinf
-#+caption: Architecture for the $\mathcal{H}_\infty\text{-synthesis}$ of three complementary filters (\subref{fig:detail_control_sensor_comp_filter_three_hinf_fb}). Bode plot of the inverse weighting functions and of the three obtained complementary filters (\subref{fig:detail_control_sensor_three_complementary_filters_results})
+#+caption: Architecture for the $\mathcal{H}_\infty$ synthesis of three complementary filters (\subref{fig:detail_control_sensor_comp_filter_three_hinf_fb}). Bode plot of the inverse weighting functions and of the three obtained complementary filters (\subref{fig:detail_control_sensor_three_complementary_filters_results})
 #+attr_latex: :options [htbp]
 #+begin_figure
 #+attr_latex: :caption \subcaption{\label{fig:detail_control_sensor_comp_filter_three_hinf_fb}Generalized plant with the synthesized filter}
 #+attr_latex: :options {0.48\textwidth}
 #+begin_subfigure
-#+attr_latex: :scale 0.9
+#+attr_latex: :width 0.95\linewidth
 [[file:figs/detail_control_sensor_comp_filter_three_hinf_fb.png]]
 #+end_subfigure
 #+attr_latex: :caption \subcaption{\label{fig:detail_control_sensor_three_complementary_filters_results}Weights and obtained filters}
@@ -2264,7 +2213,7 @@ Consider the generalized plant $P_3(s)$ shown in Figure ref:fig:detail_control_s
 #+end_subfigure
 #+end_figure
 
-Standard $\mathcal{H}_\infty\text{-synthesis}$ is performed on the generalized plant $P_3(s)$.
+Standard $\mathcal{H}_\infty$ synthesis is performed on the generalized plant $P_3(s)$.
 Two filters, $H_2(s)$ and $H_3(s)$, are obtained such that the $\mathcal{H}_\infty$ norm of the closed-loop transfer from $w$ to $[z_1,\ z_2,\ z_3]$ of the system in Figure ref:fig:detail_control_sensor_comp_filter_three_hinf_fb is less than one.
 Filter $H_1(s)$ is defined using eqref:eq:detail_control_sensor_h1_compl_h2_h3, thus ensuring the complementary property of the obtained set of filters.
 
@@ -2325,13 +2274,13 @@ exportFig('figs/detail_control_sensor_three_complementary_filters_results.pdf',
 :UNNUMBERED: t
 :END:
 
-A new method for designing complementary filters using the $\mathcal{H}_\infty\text{-synthesis}$ has been proposed.
+A new method for designing complementary filters using the $\mathcal{H}_\infty$ synthesis has been proposed.
 This approach allows shaping of the filter magnitudes through the use of weighting functions during synthesis.
 This capability is particularly valuable in practice since the characteristics of the super sensor are directly linked to the complementary filters' magnitude.
 Consequently, typical sensor fusion objectives can be effectively translated into requirements on the magnitudes of the filters.
 
-For the NASS, the HAC-LAC strategy was found to perform well and to offer the advantages of being both intuitive to understand and straightforward to tune.
+For the Nano Active Stabilization System (NASS), the High Authority Control-Integral Force Feedback (HAC-IFF) strategy was found to perform well and to offer the advantages of being both intuitive to understand and straightforward to tune.
-Looking forward, it would be interesting to investigate how sensor fusion (particularly between the force sensors and external metrology) compares to the HAC-IFF approach in terms of performance and robustness.
+Looking forward, it would be interesting to investigate how sensor fusion (particularly between the force sensor and external metrology) compares to the HAC-IFF approach in terms of performance and robustness.
 
 * Decoupling
 :PROPERTIES:
@@ -2341,7 +2290,7 @@ Looking forward, it would be interesting to investigate how sensor fusion (parti
 
 ** Introduction                                                      :ignore:
 
-The control of parallel manipulators (and any MIMO system in general) typically involves a two-step approach: first decoupling the plant dynamics (using various strategies discussed in this section), followed by the application of SISO control for the decoupled plant (discussed in section ref:sec:detail_control_cf).
+The control of parallel manipulators (and any MIMO system in general) typically involves a two-step approach: first decoupling the plant dynamics using various strategies, which will be discussed in this section, followed by the application of SISO control for the decoupled plant (discussed in section ref:sec:detail_control_cf).
 
 When sensors are integrated within the struts, decentralized control may be applied, as the system is already well decoupled at low frequency.
 For instance, [[cite:&furutani04_nanom_cuttin_machin_using_stewar]] implemented a system where each strut consists of piezoelectric stack actuators and eddy current displacement sensors, with separate PI controllers for each strut.
@@ -2353,24 +2302,23 @@ This approach enables the implementation of controllers in a defined frame.
 It has been applied with various sensor types including force sensors [[cite:&mcinroy00_desig_contr_flexur_joint_hexap]], relative displacement sensors [[cite:&kim00_robus_track_contr_desig_dof_paral_manip]], and inertial sensors [[cite:&li01_simul_vibrat_isolat_point_contr;&abbas14_vibrat_stewar_platf]].
 The Cartesian frame in which the system is decoupled is typically chosen at the point of interest (i.e., where the motion is of interest) or at the center of mass.
 
-Modal decoupling represents another noteworthy decoupling strategy, wherein the "local" plant inputs and outputs are mapped to the modal space.
+Modal control represents another noteworthy decoupling strategy, wherein the "local" plant inputs and outputs are mapped to the modal space.
 In this approach, multiple SISO plants, each corresponding to a single mode, can be controlled independently.
 This decoupling strategy has been implemented for active damping applications [[cite:&holterman05_activ_dampin_based_decoup_colloc_contr]], which is logical as it is often desirable to dampen specific modes.
 The strategy has also been employed in [[cite:&pu11_six_degree_of_freed_activ]] for vibration isolation purposes using geophones, and in [[cite:&yang19_dynam_model_decoup_contr_flexib]] using force sensors.
 
-Another completely different strategy would be to implement a multivariable control directly on the coupled system.
+Another completely different strategy, is to use implement a multivariable control directly on the coupled system.
 $\mathcal{H}_\infty$ and $\mu\text{-synthesis}$ were applied to a Stewart platform model in [[cite:&lei08_multi_objec_robus_activ_vibrat]].
-In [[cite:&xie17_model_contr_hybrid_passiv_activ]], decentralized force feedback was first applied, followed by $\mathcal{H}_2\text{-synthesis}$ for vibration isolation based on accelerometers.
+In [[cite:&xie17_model_contr_hybrid_passiv_activ]], decentralized force feedback was first applied, followed by $\mathcal{H}_2$ synthesis for vibration isolation based on accelerometers.
-$\mathcal{H}_\infty\text{-synthesis}$ was also employed in [[cite:&jiao18_dynam_model_exper_analy_stewar]] for active damping based on accelerometers.
+$\mathcal{H}_\infty$ synthesis was also employed in [[cite:&jiao18_dynam_model_exper_analy_stewar]] for active damping based on accelerometers.
-A comparative study between $\mathcal{H}_\infty\text{-synthesis}$ and decentralized control in the frame of the struts was performed in [[cite:&thayer02_six_axis_vibrat_isolat_system]].
+[[cite:&thayer02_six_axis_vibrat_isolat_system]] compared $\mathcal{H}_\infty$ synthesis with decentralized control in the frame of the struts.
 Their experimental closed-loop results indicated that the $\mathcal{H}_\infty$ controller did not outperform the decentralized controller in the frame of the struts.
-These limitations were attributed to the model's poor ability to predict off-diagonal dynamics, which is crucial for $\mathcal{H}_\infty\text{-synthesis}$.
+These limitations were attributed to the model's poor ability to predict off-diagonal dynamics, which is crucial for $\mathcal{H}_\infty$ synthesis.
 
 The purpose of this section is to compare several methods for the decoupling of parallel manipulators, an analysis that appears to be lacking in the literature.
-A simplified parallel manipulator model is introduced in Section ref:ssec:detail_control_decoupling_model as a test case for evaluating decoupling strategies.
+The analysis begins in Section ref:ssec:detail_control_decoupling_model with the introduction of a simplified parallel manipulator model that serves as the foundation for evaluating various decoupling strategies.
-The decentralized plant (transfer functions from actuators to sensors integrated in the struts) is examined in Section ref:ssec:detail_control_decoupling_decentralized.
+Sections ref:ssec:detail_control_decoupling_jacobian through ref:ssec:detail_control_decoupling_svd systematically examine three distinct approaches: Jacobian matrix decoupling, modal decoupling, and Singular Value Decomposition (SVD) decoupling, respectively.
-Three approaches are investigated across subsequent sections: Jacobian matrix decoupling (Section ref:ssec:detail_control_decoupling_jacobian), modal decoupling (Section ref:ssec:detail_control_decoupling_modal), and Singular Value Decomposition (SVD) decoupling (Section ref:ssec:detail_control_decoupling_svd).
+The comparative assessment of these three methodologies, along with concluding observations, is provided in Section ref:ssec:detail_control_decoupling_comp.
-Finally, a comparative analysis with concluding observations is provided in Section ref:ssec:detail_control_decoupling_comp.
 
 ** Matlab Init                                              :noexport:ignore:
 #+begin_src matlab :tangle no :exports none :results silent :noweb yes :var current_dir=(file-name-directory buffer-file-name)
@@ -2492,11 +2440,24 @@ The dynamics in the frame of the struts are first examined.
 The equation of motion relating actuator forces $\bm{\mathcal{\tau}}$ to strut relative motion $\bm{\mathcal{L}}$ is derived from equation eqref:eq:detail_control_decoupling_plant_cartesian by mapping the Cartesian motion of the mass to the relative motion of the struts using the Jacobian matrix $\bm{J}_{\{M\}}$ defined in eqref:eq:detail_control_decoupling_jacobian_CoM.
 The obtained transfer function from $\bm{\mathcal{\tau}}$ to $\bm{\mathcal{L}}$ is shown in eqref:eq:detail_control_decoupling_plant_decentralized.
 
+#+begin_src latex :file detail_control_decoupling_control_struts.pdf
+\begin{tikzpicture}
+  \node[block] (Gl) {$\bm{G}_{\{\mathcal{L}\}}$};
+
+  % Connections and labels
+  \draw[<-] (Gl.west) -- ++(-0.8, 0) node[above right]{$\bm{\tau}$};
+  \draw[->] (Gl.east) -- ++( 0.8, 0) node[above left]{$\bm{\mathcal{L}}$};
+\end{tikzpicture}
+#+end_src
+
+#+RESULTS:
+# [[file:figs/detail_control_decoupling_control_struts.png]]
+
 \begin{equation}\label{eq:detail_control_decoupling_plant_decentralized}
   \frac{\bm{\mathcal{L}}}{\bm{\mathcal{\tau}}}(s) = \bm{G}_{\mathcal{L}}(s) = \left( \bm{J}_{\{M\}}^{-\intercal} \bm{M}_{\{M\}} \bm{J}_{\{M\}}^{-1} s^2 + \bm{\mathcal{C}} s + \bm{\mathcal{K}} \right)^{-1}
 \end{equation}
 
-At low frequencies, the plant converges to a diagonal constant matrix whose diagonal elements are equal to the actuator stiffnesses eqref:eq:detail_control_decoupling_plant_decentralized_low_freq.
+At low frequencies, the plant converges to a diagonal constant matrix whose diagonal elements are related to the actuator stiffnesses eqref:eq:detail_control_decoupling_plant_decentralized_low_freq.
 At high frequencies, the plant converges to the mass matrix mapped in the frame of the struts, which is generally highly non-diagonal.
 
 \begin{equation}\label{eq:detail_control_decoupling_plant_decentralized_low_freq}
@@ -2564,7 +2525,7 @@ for out_i = 1:3
         xlim([freqs(1), freqs(end)]); ylim([2e-8, 4e-5]);
         xticks([1e0, 1e1, 1e2])
         yticks([1e-7, 1e-6, 1e-5])
-        leg = legend('location', 'northeast', 'FontSize', 8);
+        leg = legend('location', 'southwest', 'FontSize', 8);
         leg.ItemTokenSize(1) = 18;
 
         if in_i == 1
@@ -2595,7 +2556,7 @@ exportFig('figs/detail_control_decoupling_coupled_plant_bode.pdf', 'width', 'ful
 <<ssec:detail_control_decoupling_jacobian>>
 **** Jacobian Matrix
 
-The Jacobian matrix $\bm{J}_{\{O\}}$ serves a dual purpose in the decoupling process: it converts strut velocity $\dot{\mathcal{L}}$ to payload velocity and angular velocity $\dot{\bm{\mathcal{X}}}_{\{O\}}$, and it transforms actuator forces $\bm{\tau}$ to forces/torque applied on the payload $\bm{\mathcal{F}}_{\{O\}}$, as expressed in equation eqref:eq:detail_control_decoupling_jacobian.
+The Jacobian matrix serves a dual purpose in the decoupling process: it converts strut velocity $\dot{\mathcal{L}}$ to payload velocity and angular velocity $\dot{\bm{\mathcal{X}}}_{\{O\}}$, and it transforms actuator forces $\bm{\tau}$ to forces/torque applied on the payload $\bm{\mathcal{F}}_{\{O\}}$, as expressed in equation eqref:eq:detail_control_decoupling_jacobian.
 
 \begin{subequations}\label{eq:detail_control_decoupling_jacobian}
   \begin{align}
@@ -2657,6 +2618,28 @@ When the decoupling frame is located at the center of mass (frame $\{M\}$ in Fig
   \end{bmatrix}
 \end{equation}
 
+#+begin_src latex :file detail_control_decoupling_control_jacobian_CoM.pdf
+\begin{tikzpicture}
+  \node[block] (G) {$\bm{G}_{\{\mathcal{L}\}}$};
+  \node[block, left=0.6 of G] (Jt) {$\bm{J}_{\{M\}}^{-\intercal}$};
+  \node[block, right=0.6 of G] (Ja) {$\bm{J}_{\{M\}}^{-1}$};
+
+  % Connections and labels
+  \draw[<-] (Jt.west) -- ++(-1.4, 0) node[above right]{$\bm{\mathcal{F}}_{\{M\}}$};
+  \draw[->] (Jt.east) -- (G.west)  node[above left]{$\bm{\tau}$};
+  \draw[->] (G.east) -- (Ja.west)  node[above left]{$\bm{\mathcal{L}}$};
+  \draw[->] (Ja.east) -- ++( 1.4, 0)  node[above left]{$\bm{\mathcal{X}}_{\{M\}}$};
+
+  \begin{scope}[on background layer]
+    \node[fit={(Jt.south west) (Ja.north east)}, fill=black!10!white, draw, dashed, inner sep=4pt] (Gx) {};
+    \node[above] at (Gx.north) {$\bm{G}_{\{M\}}$};
+  \end{scope}
+\end{tikzpicture}
+#+end_src
+
+#+RESULTS:
+# [[file:figs/detail_control_decoupling_control_jacobian_CoM.png]]
+
 Analytical formula of the plant $\bm{G}_{\{M\}}(s)$ is derived eqref:eq:detail_control_decoupling_plant_CoM.
 
 \begin{equation}\label{eq:detail_control_decoupling_plant_CoM}
@@ -2730,6 +2713,28 @@ exportFig('figs/detail_control_decoupling_jacobian_plant_CoM.pdf', 'width', 'hal
 
 **** Center Of Stiffness
 
+#+begin_src latex :file detail_control_decoupling_control_jacobian_CoK.pdf
+\begin{tikzpicture}
+  \node[block] (G) {$\bm{G}_{\{\mathcal{L}\}}$};
+  \node[block, left=0.6 of G] (Jt) {$\bm{J}_{\{K\}}^{-\intercal}$};
+  \node[block, right=0.6 of G] (Ja) {$\bm{J}_{\{K\}}^{-1}$};
+
+  % Connections and labels
+  \draw[<-] (Jt.west) -- ++(-1.4, 0) node[above right]{$\bm{\mathcal{F}}_{\{K\}}$};
+  \draw[->] (Jt.east) -- (G.west)  node[above left]{$\bm{\tau}$};
+  \draw[->] (G.east) -- (Ja.west)  node[above left]{$\bm{\mathcal{L}}$};
+  \draw[->] (Ja.east) -- ++( 1.4, 0)  node[above left]{$\bm{\mathcal{X}}_{\{K\}}$};
+
+  \begin{scope}[on background layer]
+    \node[fit={(Jt.south west) (Ja.north east)}, fill=black!10!white, draw, dashed, inner sep=4pt] (Gx) {};
+    \node[above] at (Gx.north) {$\bm{G}_{\{K\}}$};
+  \end{scope}
+\end{tikzpicture}
+#+end_src
+
+#+RESULTS:
+# [[file:figs/detail_control_decoupling_control_jacobian_CoK.png]]
+
 When the decoupling frame is located at the center of stiffness, the Jacobian matrix and its inverse are expressed as in eqref:eq:detail_control_decoupling_jacobian_CoK_inverse.
 
 \begin{equation}\label{eq:detail_control_decoupling_jacobian_CoK_inverse}
@@ -2749,7 +2754,7 @@ However, it could alternatively be determined through analytical methods to ensu
 It should be noted that the existence of such a center of stiffness (i.e. a frame $\{K\}$ for which $\bm{J}_{\{K\}}^{\intercal} \bm{\mathcal{K}} \bm{J}_{\{K\}}$ is diagonal) is not guaranteed for arbitrary systems.
 This property is typically achievable only in systems exhibiting specific symmetrical characteristics, as is the case in the present example.
 
-The analytical expression for the plant in this configuration was then computed eqref:eq:detail_control_decoupling_plant_CoK.
+The analytical expression for the plant in this configuration was then computed ref:eq:detail_control_decoupling_plant_CoK.
 
 \begin{equation}\label{eq:detail_control_decoupling_plant_CoK}
   \frac{\bm{\mathcal{X}}_{\{K\}}}{\bm{\mathcal{F}}_{\{K\}}}(s) = \bm{G}_{\{K\}}(s) = \left( \bm{J}_{\{K\}}^{\intercal} \bm{J}_{\{M\}}^{-\intercal} \bm{M}_{\{M\}} \bm{J}_{\{M\}}^{-1} \bm{J}_{\{K\}} s^2 + \bm{J}_{\{K\}}^{\intercal} \bm{\mathcal{C}} \bm{J}_{\{K\}} s + \bm{J}_{\{K\}}^{\intercal} \bm{\mathcal{K}} \bm{J}_{\{K\}} \right)^{-1}
@@ -2765,6 +2770,7 @@ The plant is well decoupled below the suspension mode with the lowest frequency
 
 The physical reason for high-frequency coupling is illustrated in Figure ref:fig:detail_control_decoupling_model_test_CoK.
 When a high-frequency force is applied at a point not aligned with the center of mass, it induces rotation around the center of mass.
+This phenomenon explains the coupling observed between different degrees of freedom at higher frequencies.
 
 #+begin_src matlab
 %% Jacobian Decoupling - Center of Mass
@@ -2828,6 +2834,7 @@ exportFig('figs/detail_control_decoupling_jacobian_plant_CoK.pdf', 'width', 'hal
 **** Theory                                                        :ignore:
 
 Modal decoupling represents an approach based on the principle that a mechanical system's behavior can be understood as a combination of contributions from various modes [[cite:&rankers98_machin]].
+
 To convert the dynamics in the modal space, the equation of motion are first written with respect to the center of mass eqref:eq:detail_control_decoupling_equation_motion_CoM.
 
 \begin{equation}\label{eq:detail_control_decoupling_equation_motion_CoM}
@@ -2966,7 +2973,7 @@ exportFig('figs/detail_control_decoupling_modal_plant.pdf', 'width', 'half', 'he
 <<ssec:detail_control_decoupling_svd>>
 **** Singular Value Decomposition
 
-Singular Value Decomposition (SVD) represents a powerful mathematical tool with extensive applications in data analysis [[cite:&brunton22_data, chapt. 1]] and multivariable control systems where it is particularly valuable for analyzing directional properties in multivariable systems [[cite:&skogestad07_multiv_feedb_contr]].
+Singular Value Decomposition (SVD) represents a powerful mathematical tool with extensive applications in data analysis [[cite:&brunton22_data, chapt. 1]] and multivariable control systems [[cite:&skogestad07_multiv_feedb_contr]], where it is particularly valuable for analyzing directional properties in multivariable systems.
 
 The SVD constitutes a unique matrix decomposition applicable to any complex matrix $\bm{X} \in \mathbb{C}^{n \times m}$, expressed as:
 
@@ -3104,8 +3111,8 @@ exportFig('figs/detail_control_decoupling_svd_plant.pdf', 'width', 'wide', 'heig
 [[file:figs/detail_control_decoupling_svd_plant.png]]
 
 As it was surprising to obtain such a good decoupling at all frequencies, a variant system with identical dynamics but different sensor configurations was examined.
-Instead of using relative motion sensors collocated with the struts, three relative motion sensors were positioned as shown in Figure ref:fig:detail_control_decoupling_model_test_alt.
+Instead of using relative motion sensors aligned with the struts, three relative motion sensors were positioned as shown in Figure ref:fig:detail_control_decoupling_model_test_alt.
-Although Jacobian matrices could theoretically be used to map these sensors to the frame of the struts, application of the same SVD decoupling procedure yielded the plant response shown in Figure ref:fig:detail_control_decoupling_svd_alt_plant, which exhibits significantly greater coupling.
+Although Jacobian matrices could theoretically map between these different sensor arrangements, application of the same SVD decoupling procedure yielded the plant response shown in Figure ref:fig:detail_control_decoupling_svd_alt_plant, which exhibits significantly greater coupling.
 Notably, the coupling demonstrates local minima near the decoupling frequency, consistent with the fact that the decoupling matrices were derived specifically for that frequency point.
 
 #+begin_src matlab
@@ -3213,7 +3220,8 @@ SVD decoupling generally results in a loss of physical meaning for the "control
 The quality of decoupling achieved through these methods also exhibits distinct characteristics.
 Jacobian decoupling performance depends on the chosen reference frame, with optimal decoupling at low frequencies when aligned at the center of stiffness, or at high frequencies when aligned with the center of mass.
 Systems designed with coincident centers of mass and stiffness may achieve excellent decoupling using this approach.
-Modal decoupling offers good decoupling across all frequencies, though its effectiveness relies on the model accuracy, with discrepancies potentially resulting in significant off-diagonal elements.
+Modal decoupling offers good decoupling across all frequencies, though its effectiveness relies on the accuracy of the system model, with discrepancies potentially resulting in significant off-diagonal elements.
+The diagonal elements typically manifest as second-order low-pass filters, facilitating straightforward control design.
 SVD decoupling can be implemented using measured data without requiring a model, with optimal performance near the chosen decoupling frequency, though its effectiveness may diminish at other frequencies and depends on the quality of the real approximation of the response at the selected frequency point.
 
 #+name: tab:detail_control_decoupling_strategies_comp
@@ -3221,24 +3229,34 @@ SVD decoupling can be implemented using measured data without requiring a model,
 #+attr_latex: :environment tabularx :width \linewidth :align lXXX
 #+attr_latex: :center t :booktabs t :font \scriptsize
 |                       | *Jacobian*                                                                             | *Modal*                                                               | *SVD*                                                            |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
 | *Philosophy*          | Topology Driven                                                                        | Physics Driven                                                        | Data Driven                                                      |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
 | *Requirements*        | Known geometry                                                                         | Known equations of motion                                             | Identified FRF                                                   |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
-| *Decoupling Matrices* | Jacobian matrix $\bm{J}_{\{O\}}$                                                              | Eigenvectors $\bm{\Phi}$                                                                     | SVD matrices $\bm{U}$ and $\bm{V}$                                                                 |
+| *Decoupling Matrices* | Decoupling using $\bm{J}_{\{O\}}$ obtained from geometry                               | Decoupling using $\bm{\Phi}$ obtained from modal decomposition        | Decoupling using $\bm{U}$ and $\bm{V}$ obtained from SVD         |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
 | *Decoupled Plant*     | $\bm{G}_{\{O\}}(s) = \bm{J}_{\{O\}}^{-1} \bm{G}_{\mathcal{L}}(s) \bm{J}_{\{O\}}^{-\intercal}$ | $\bm{G}_m(s) = \bm{\Phi}^{-1} \bm{G}_{\mathcal{X}}(s) \bm{\Phi}^{-\intercal}$ | $\bm{G}_{\text{SVD}}(s) = \bm{U}^{-1} \bm{G}(s) \bm{V}^{-\intercal}$ |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
 | *Controller*          | $\bm{K}_{\{O\}}(s) = \bm{J}_{\{O\}}^{-\intercal} \bm{K}_{d}(s) \bm{J}_{\{O\}}^{-1}$   | $\bm{K}_m(s) = \bm{\Phi}^{-\intercal} \bm{K}_{d}(s) \bm{\Phi}^{-1}$  | $\bm{K}_{\text{SVD}}(s) = \bm{V}^{-\intercal} \bm{K}_{d}(s) \bm{U}^{-1}$ |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
-| *Interpretation*      | Forces/Torques to Displacement/Rotation in chosen frame                                       | Inputs (resp. outputs) to excite (resp. sense) individual modes                              | Directions of max to min controllability/observability                                             |
+| *Interpretation*      | Forces/Torques to Displacement/Rotation in chosen frame                                | Inputs to excite individual modes                                     | Directions of max to min controllability/observability           |
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+|                       |                                                                                        | Output to sense individual modes                                      |                                                                  |
-| *Effectiveness*       | Decoupling at low or high frequency depending on the chosen frame                             | Good decoupling at all frequencies                                                           | Good decoupling near the chosen frequency                                                          |
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+| *Properties*          | Decoupling at low or high frequency depending on the chosen frame                      | Good decoupling at all frequencies                                    | Good decoupling near the chosen frequency                        |
-| *Pros*                | Retain physical meaning of inputs / outputs. Controller acts on a meaningfully "frame"        | Ability to target specific modes. Simple $2^{nd}$ order diagonal plants                      | Good Decoupling near the crossover. Very General and requires no model                             |
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
-|-----------------------+-----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------+----------------------------------------------------------------------------------------------------|
+| *Pros*                | Physical inputs / outputs                                                              | Target specific modes                                                 | Good Decoupling near the crossover                               |
-| *Cons*                | Good decoupling at all frequency can only be obtained for specific mechanical architecture    | Relies on the accuracy of equation of motions. Robustness to unmodelled dynamics may be poor | Loss of physical meaning of inputs /outputs. Decoupling away from the chosen frequency may be poor |
+|                       | Good decoupling at High frequency (diagonal mass matrix if Jacobian taken at the CoM)  | 2nd order diagonal plant                                              | Very General                                                     |
+|                       | Good decoupling at Low frequency (if Jacobian taken at specific point)                 |                                                                       |                                                                  |
+|                       | Easy integration of meaningful reference inputs                                        |                                                                       |                                                                  |
+|                       |                                                                                        |                                                                       |                                                                  |
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
+| *Cons*                | Coupling between force/rotation may be high at low frequency (non diagonal terms in K) | Need analytical equations                                             | Loose the physical meaning of inputs /outputs                    |
+|                       | Limited to parallel mechanisms (?)                                                     |                                                                       | Decoupling depends on the real approximation validity            |
+|                       | If good decoupling at all frequencies => requires specific mechanical architecture     |                                                                       | Diagonal plants may not be easy to control                       |
+|-----------------------+----------------------------------------------------------------------------------------+-----------------------------------------------------------------------+------------------------------------------------------------------|
+| *Applicability*       | Parallel Mechanisms                                                                    | Systems whose dynamics that can be expressed with M and K matrices    | Very general                                                     |
+|                       | Only small motion for the Jacobian matrix to stay constant                             |                                                                       | Need FRF data (either experimentally or analytically)            |
 
 * Closed-Loop Shaping using Complementary Filters
 :PROPERTIES:
@@ -3251,23 +3269,27 @@ SVD decoupling can be implemented using measured data without requiring a model,
 Once the system is properly decoupled using one of the approaches described in Section ref:sec:detail_control_decoupling, SISO controllers can be individually tuned for each decoupled "directions".
 Several ways to design a controller to obtain a given performance while ensuring good robustness properties can be implemented.
 
-In some cases "fixed" controller structures are utilized, such as PI and PID controllers, whose parameters are manually tuned [[cite:&furutani04_nanom_cuttin_machin_using_stewar;&du14_piezo_actuat_high_precis_flexib;&yang19_dynam_model_decoup_contr_flexib]].
+# Add reference
+In some cases, "fixed" controller structures are utilized, such as PI and PID controllers [[cite:&furutani04_nanom_cuttin_machin_using_stewar;&du14_piezo_actuat_high_precis_flexib;&yang19_dynam_model_decoup_contr_flexib]].
+In such cases, the controller coefficients are manually tuned to obtain acceptable performance and robustness.
 
-Another popular method is Open-Loop shaping, which was used during the conceptual phase.
+Another popular method is Open-Loop shaping, that was used during the conceptual phase after the plan was decoupled in the frame of the struts.
-Open-loop shaping involves tuning the controller through a series of "standard" filters (leads, lags, notches, low-pass filters, ...) to shape the open-loop transfer function $G(s)K(s)$ according to desired specifications, including bandwidth, gain and phase margins [[cite:&schmidt20_desig_high_perfor_mechat_third_revis_edition, chapt. 4.4.7]].
+The idea of open-loop shaping is to tune the controller (using a series of standard leads, lags, notches, low pass filters) such that the open-loop transfer function $G(s)K(s)$ is made according to specification (i.e.
-Open-Loop shaping is very popular because the open-loop transfer function is a linear function of the controller, making it relatively straightforward to tune the controller to achieve desired open-loop characteristics.
+bandwidth, gain and phase margins, gain at a specific frequency, etc...) [[cite:&schmidt20_desig_high_perfor_mechat_third_revis_edition, chapt. 4.4.7]].
-Another key advantage is that controllers can be tuned directly from measured frequency response functions of the plant without requiring an explicit model.
+Open-Loop shaping is very popular because the open-loop transfer function depends linearly on the controller, making it relatively straightforward to tune the controller to achieve desired open-loop characteristics.
+Another key advantage is that controllers can be tuned directly from measured frequency response functions without requiring an explicit plant model.
 
-However, the behavior (i.e. performance) of a feedback system is a function of closed-loop transfer functions.
+However, the behavior (i.e. performance) of a feedback system is a function of closed-loop transfer functions [[cite:&skogestad07_multiv_feedb_contr, chapt. 3]].
-Specifications can therefore be expressed in terms of the magnitude of closed-loop transfer functions, such as the sensitivity, plant sensitivity, and complementary sensitivity transfer functions [[cite:&skogestad07_multiv_feedb_contr, chapt. 3]].
+Specifications can therefore be expressed in terms of the magnitude of closed-loop transfer functions, such as the sensitivity, plant sensitivity, and complementary sensitivity transfer functions.
 With open-loop shaping, closed-loop transfer functions are changed only indirectly, which may make it difficult to directly address the specifications that are in terms of the closed-loop transfer functions.
 
-In order to synthesize a controller that directly shapes the closed-loop transfer functions (and therefore the performance metric), $\mathcal{H}_\infty\text{-synthesis}$ may be used [[cite:&skogestad07_multiv_feedb_contr]].
+In order to synthesize a controller that directly shapes the closed-loop transfer functions (and therefore the performance metric), $\mathcal{H}_\infty$ loop-shaping may be used [[cite:&skogestad07_multiv_feedb_contr]].
 This approach requires a good model of the plant and expertise in selecting weighting functions that will define the wanted shape of different closed-loop transfer functions [[cite:&bibel92_guidel_h]].
-$\mathcal{H}_{\infty}\text{-synthesis}$ has been applied for the Stewart platform [[cite:&jiao18_dynam_model_exper_analy_stewar]], yet when benchmarked against more basic decentralized controllers, the performance gains proved small [[cite:&thayer02_six_axis_vibrat_isolat_system;&hauge04_sensor_contr_space_based_six]].
+$\mathcal{H}_{\infty}$ synthesis has been applied for the Stewart platform [[cite:&jiao18_dynam_model_exper_analy_stewar]], but comparative studies with more simple decentralized controllers did not show large improvements [[cite:&thayer02_six_axis_vibrat_isolat_system;&hauge04_sensor_contr_space_based_six]].
 
 In this section, an alternative controller synthesis scheme is proposed in which complementary filters are used for directly shaping the closed-loop transfer functions (i.e., directly addressing the closed-loop performances).
-In Section ref:ssec:detail_control_cf_control_arch, the proposed control architecture is presented.
+
+In Section ref:ssec:detail_control_cf_control_arch, the proposed control architecture including the complementary filters is presented.
 In Section ref:ssec:detail_control_cf_trans_perf, typical performance requirements are translated into the shape of the complementary filters.
 The design of the complementary filters is briefly discussed in Section ref:ssec:detail_control_cf_analytical_complementary_filters, and analytical formulas are proposed such that it is possible to change the closed-loop behavior of the system in real time.
 Finally, in Section ref:ssec:detail_control_cf_simulations, a numerical example is used to show how the proposed control architecture can be implemented in practice.
@@ -3300,9 +3322,10 @@ freqs = logspace(-1, 3, 1000);
  <<ssec:detail_control_cf_control_arch>>
 **** Virtual Sensor Fusion
 
-The idea of using complementary filters in the control architecture originates from sensor fusion techniques [[cite:&collette15_sensor_fusion_method_high_perfor]], where two sensors are combined using complementary filters.
+The concept of using complementary filters in control architecture originates from sensor fusion techniques [[cite:&collette15_sensor_fusion_method_high_perfor]], where two sensors are combined using complementary filters.
 Building upon this concept, "virtual sensor fusion" [[cite:&verma20_virtual_sensor_fusion_high_precis_contr]] replaces one physical sensor with a model $G$ of the plant.
-The corresponding control architecture is illustrated in Figure ref:fig:detail_control_cf_arch, where $G^\prime$ represents the physical plant to be controlled, $G$ is a model of the plant, $k$ is the controller, and $H_L$ and $H_H$ are complementary filters satisfying $H_L(s) + H_H(s) = 1$.
+
+The control architecture is illustrated in Figure ref:fig:detail_control_cf_arch, where $G^\prime$ represents the physical plant to be controlled, $G$ is a model of the plant, $k$ is the controller, and $H_L$ and $H_H$ are complementary filters satisfying $H_L(s) + H_H(s) = 1$.
 In this arrangement, the physical plant is controlled at low frequencies, while the plant model is utilized at high frequencies to enhance robustness.
 
 #+begin_src latex :file detail_control_cf_arch.pdf
@@ -3409,14 +3432,14 @@ Consequently, this structure is mathematically equivalent to the single-loop arc
 When considering the extreme case of very high values for $k$, the effective controller $K(s)$ converges to the inverse of the plant model multiplied by the inverse of the high-pass filter, as expressed in eqref:eq:detail_control_cf_high_k.
 
 \begin{equation}\label{eq:detail_control_cf_high_k}
-  \lim_{k\to\infty} K(s) = \lim_{k\to\infty} \frac{k}{1+H_H(s) G(s) k} = \big( H_H(s) G(s) \big)^{-1}
+  \lim_{k\to\infty} K(s) = \lim_{k\to\infty} \frac{k}{1+H_H(s) G(s) k} = \left( H_H(s) G(s) \right)^{-1}
 \end{equation}
 
 If the resulting $K$ is improper, a low-pass filter with sufficiently high corner frequency can be added to ensure its causal realization.
 Furthermore, for $K$ to be stable, both $G$ and $H_H$ must be minimum phase transfer functions.
 
 With these assumptions, the resulting control architecture is illustrated in Figure ref:fig:detail_control_cf_arch_class, where the complementary filters $H_L$ and $H_H$ remain the only tuning parameters.
-The dynamics of this closed-loop system are described by equations eqref:eq:detail_control_cf_cl_system_y and eqref:eq:detail_control_cf_cl_system_y.
+The dynamics of this closed-loop system are described by eqref:eq:detail_control_cf_sf_cl_tf_K_inf.
 
 #+begin_src latex :file detail_control_cf_arch_class.pdf
 \tikzset{block/.default={0.8cm}{0.6cm}}
@@ -3461,7 +3484,7 @@ The dynamics of this closed-loop system are described by equations eqref:eq:deta
   \end{align}
 \end{subequations}
 
-At frequencies where the model accurately represents the physical plant ($G^{-1} G^{\prime} \approx 1$), the denominator simplifies to $H_H + G^\prime G^{-1} H_L \approx H_H + H_L = 1$, and the closed-loop transfer functions are then described by equations eqref:eq:detail_control_cf_cl_performance_y and eqref:eq:detail_control_cf_cl_performance_u.
+At frequencies where the model accurately represents the physical plant ($G^{-1} G^{\prime} \approx 1$), the denominator simplifies to $H_H + G^\prime G^{-1} H_L \approx H_H + H_L = 1$, and the closed-loop transfer functions are described by eqref:eq:detail_control_cf_sf_cl_tf_K_inf_perfect.
 
 \begin{subequations}\label{eq:detail_control_cf_sf_cl_tf_K_inf_perfect}
   \begin{alignat}{5}
@@ -3471,16 +3494,16 @@ At frequencies where the model accurately represents the physical plant ($G^{-1}
 \end{subequations}
 
 The sensitivity transfer function equals the high-pass filter $S = \frac{y}{dy} = H_H$, and the complementary sensitivity transfer function equals the low-pass filter $T = \frac{y}{n} = H_L$.
-Hence, when the plant model closely approximates the actual dynamics, the closed-loop transfer functions converge to the designed complementary filters, allowing direct translation of performance requirements into the design of the complementary.
+Hence, when the plant model closely approximates the actual system, the closed-loop behavior becomes fully determined by the designed complementary filters, enabling direct translation of performance requirements into filter design.
 
-** Translating the performance requirements into the shape of the complementary filters
+** Translating the performance requirements into the shapes of the complementary filters
  <<ssec:detail_control_cf_trans_perf>>
 **** Introduction                                                  :ignore:
-Performance specifications in a feedback system can usually be expressed as upper bounds on the magnitudes of closed-loop transfer functions such as the sensitivity and complementary sensitivity transfer functions [[cite:&bibel92_guidel_h]].
+Performance specifications in feedback systems can be expressed as upper bounds on the magnitudes of closed-loop transfer functions such that the sensitivity $|S(j\omega)|$ and complementary sensitivity $|T(j\omega)|$ transfer functions [[cite:&bibel92_guidel_h]].
-The design of a controller $K(s)$ to obtain the desired shape of these closed-loop transfer functions is known as closed-loop shaping.
+The design of a controller $K(s)$ to achieve desired shapes of these closed-loop transfer functions is known as closed-loop shaping.
 
 In the proposed control architecture, the closed-loop transfer functions eqref:eq:detail_control_cf_sf_cl_tf_K_inf are expressed in terms of the complementary filters $H_L(s)$ and $H_H(s)$ rather than directly through the controller $K(s)$.
-Therefore, performance requirements must be translated into constraints on the shape of these complementary filters.
+Therefore, performance requirements must be translated into constraints on the shapes of these complementary filters.
 
 **** Nominal Stability (NS)
 A closed-loop system is stable when all its elements (here $K$, $G^\prime$, and $H_L$) are stable and the sensitivity function $S = \frac{1}{1 + G^\prime K H_L}$ is stable.
@@ -3492,7 +3515,6 @@ Consequently, stable and minimum phase complementary filters must be employed.
 **** Nominal Performance (NP)
 
 Performance specifications can be formalized using weighting functions $w_H$ and $w_L$, where performance is achieved when eqref:eq:detail_control_cf_weights is satisfied.
-The weighting functions define the maximum magnitude of the closed-loop transfer functions as a function of frequency, effectively determining their "shape".
 
 \begin{subequations}\label{eq:detail_control_cf_weights}
   \begin{align}
@@ -3501,7 +3523,7 @@ The weighting functions define the maximum magnitude of the closed-loop transfer
   \end{align}
 \end{subequations}
 
-For the nominal system, $S = H_H$ and $T = H_L$, hence the performance specifications can be converted on the shape of the complementary filters eqref:eq:detail_control_cf_nominal_performance.
+For the nominal system, where $S = H_H$ and $T = H_L$, nominal performance is ensured by satisfying eqref:eq:detail_control_cf_nominal_performance.
 
 \begin{equation}\label{eq:detail_control_cf_nominal_performance}
 \Aboxed{\text{NP} \Longleftrightarrow {\begin{cases*}
@@ -3510,20 +3532,23 @@ For the nominal system, $S = H_H$ and $T = H_L$, hence the performance specifica
   \end{cases*}}}
 \end{equation}
 
+Typical performance requirements can therefore be translated into constraints on the complementary filters.
 For disturbance rejection, the magnitude of the sensitivity function $|S(j\omega)| = |H_H(j\omega)|$ should be minimized, particularly at low frequencies where disturbances are usually most prominent.
 Similarly, for noise attenuation, the magnitude of the complementary sensitivity function $|T(j\omega)| = |H_L(j\omega)|$ should be minimized, especially at high frequencies where measurement noise typically dominates.
+The closed-loop bandwidth can be effectively limited by ensuring that $|T(j\omega)|$ remains below $\frac{1}{\sqrt{2}}$ at frequencies above the maximum desired bandwidth.
+By carefully selecting the shapes of these complementary filters, nominal performance specifications can be directly addressed in an intuitive manner.
+
 Classical stability margins (gain and phase margins) are also related to the maximum amplitude of the sensitivity transfer function.
 Typically, maintaining $|S|_{\infty} \le 2$ ensures a gain margin of at least 2 and a phase margin of at least $\SI{29}{\degree}$.
 
-Therefore, by carefully selecting the shape of the complementary filters, nominal performance specifications can be directly addressed in an intuitive manner.
-
 **** Robust Stability (RS)
 
 Robust stability refers to a control system's ability to maintain stability despite discrepancies between the actual system $G^\prime$ and the model $G$ used for controller design.
 These discrepancies may arise from unmodeled dynamics or nonlinearities.
 
 To represent these model-plant differences, input multiplicative uncertainty as illustrated in Figure ref:fig:detail_control_cf_input_uncertainty is employed.
-The set of possible plants $\Pi_i$ is described by eqref:eq:detail_control_cf_multiplicative_uncertainty, with the weighting function $w_I$ selected such that all possible plants $G^\prime$ are contained within the set $\Pi_i$.
+The set of possible plants $\Pi_i$ is described by eqref:eq:detail_control_cf_multiplicative_uncertainty.
+With the weighting function $w_I$ selected such that all possible plants $G^\prime$ are contained within the set $\Pi_i$.
 
 \begin{equation}\label{eq:detail_control_cf_multiplicative_uncertainty}
   \Pi_i: \quad G^\prime(s) = G(s)\big(1 + w_I(s)\Delta_I(s)\big); \quad |\Delta_I(j\omega)| \le 1 \ \forall\omega
@@ -3591,7 +3616,8 @@ After algebraic manipulation, robust stability is guaranteed when the low-pass c
 
 **** Robust Performance (RP)
 
-Robust performance ensures that performance specifications eqref:eq:detail_control_cf_weights are met even when the plant dynamics fluctuates within specified bounds eqref:eq:detail_control_cf_robust_perf_S.
+Robust performance ensures that performance specifications eqref:eq:detail_control_cf_weights are met even as plant dynamics varies within specified bounds.
+This requires the performance condition to be valid for all possible plants in the defined uncertainty set $\Pi_i$:
 
 \begin{equation}\label{eq:detail_control_cf_robust_perf_S}
   \text{RP} \Longleftrightarrow |w_H(j\omega) S(j\omega)| \le 1 \quad \forall G^\prime \in \Pi_I, \ \forall\omega
@@ -3610,8 +3636,8 @@ Therefore, for SISO systems, ensuring robust stability and nominal performance i
 ** Complementary filter design
 <<ssec:detail_control_cf_analytical_complementary_filters>>
 
-As proposed in Section ref:sec:detail_control_sensor, complementary filters can be shaped using standard $\mathcal{H}_{\infty}\text{-synthesis}$ techniques.
+As proposed in Section ref:sec:detail_control_sensor, complementary filters can be shaped using standard $\mathcal{H}_{\infty}$ synthesis techniques.
-This approach is particularly well-suited since performance requirements were expressed as upper bounds on the magnitude of the complementary filters.
+This approach is particularly well-suited since performance requirements were expressed as upper bounds on the magnitude of the complementary filters (Section ref:ssec:detail_control_cf_trans_perf).
 
 Alternatively, analytical formulas for complementary filters may be employed.
 For some applications, first-order complementary filters as shown in Equation eqref:eq:detail_control_cf_1st_order are sufficient.
@@ -3632,7 +3658,7 @@ These filters can be transformed into the digital domain using the Bilinear tran
   \end{align}
 \end{subequations}
 
-A significant advantage of using analytical formulas for complementary filters is that key parameters such as $\omega_0$ can be tuned in real-time, as illustrated in Figure ref:fig:detail_control_cf_arch_tunable_params.
+A significant advantage of using analytical formulas for complementary filters is that key parameters such as $\omega_0$ can be modified in real-time, as illustrated in Figure ref:fig:detail_control_cf_arch_tunable_params.
 This real-time tunability allows rapid testing of different control bandwidths to evaluate performance and robustness characteristics.
 
 #+begin_src latex :file detail_control_cf_arch_tunable_params.pdf
@@ -3680,7 +3706,7 @@ This real-time tunability allows rapid testing of different control bandwidths t
 
 For many practical applications, first order complementary filters are not sufficient.
 Specifically, a slope of $+2$ at low frequencies for the sensitivity transfer function (enabling accurate tracking of ramp inputs) and a slope of $-2$ for the complementary sensitivity transfer function are often desired.
-For these cases, the complementary filters analytical formula in Equation eqref:eq:detail_control_cf_2nd_order is proposed.
+For these cases, the second-order complementary filters presented in Equation eqref:eq:detail_control_cf_2nd_order are proposed.
 
 \begin{subequations}\label{eq:detail_control_cf_2nd_order}
   \begin{align}
@@ -3690,15 +3716,18 @@ For these cases, the complementary filters analytical formula in Equation eqref:
 \end{subequations}
 
 The influence of parameters $\alpha$ and $\omega_0$ on the frequency response of these complementary filters is illustrated in Figure ref:fig:detail_control_cf_analytical_effect.
-The parameter $\alpha$ primarily affects the damping characteristics near the crossover frequency as well as high and low frequency magnitudes, while $\omega_0$ determines the frequency at which the transition between high-pass and low-pass behavior occurs.
+The parameter $\alpha$ primarily affects the damping characteristics near the crossover frequency, while $\omega_0$ determines the frequency at which the transition between high-pass and low-pass behavior occurs.
 These filters can also be implemented in the digital domain with analytical formulas, preserving the ability to adjust $\alpha$ and $\omega_0$ in real-time.
 
+The presented analytical formulations offer an attractive balance between design simplicity and performance.
+This capability to tune parameters in real-time is particularly valuable during commissioning of the controller.
+
 #+begin_src matlab :exports none :results none
 %% Analytical Complementary Filters - Effect of alpha
 freqs_study = logspace(-2, 2, 1000);
 alphas = [0.1, 1, 10];
 w0 = 2*pi*1;
-s = tf('s');
+s = tf('s')
 
 figure;
 hold on;
@@ -3726,7 +3755,7 @@ exportFig('figs/detail_control_cf_analytical_effect_alpha.pdf', 'width', 'half',
 freqs_study = logspace(-1, 3, 1000);
 alpha = [1];
 w0s = [2*pi*1, 2*pi*10, 2*pi*100];
-s = tf('s');
+s = tf('s')
 
 figure;
 hold on;
@@ -3771,17 +3800,17 @@ exportFig('figs/detail_control_cf_analytical_effect_w0.pdf', 'width', 'half', 'h
 <<ssec:detail_control_cf_simulations>>
 **** Procedure                                                     :ignore:
 
-To implement the proposed control architecture in practice, the following procedure is proposed:
+To systematically apply the proposed control technique, the following procedure is recommended:
 
 1. Identify the plant to be controlled to obtain the plant model $G$.
-2. Design the weighting function $w_I$ such that all possible plants $G^\prime$ are contained within the uncertainty set $\Pi_i$.
+2. Design the weighting function $w_I$ such that all possible plants $G^\prime$ are contained in the uncertainty set $\Pi_i$.
 3. Translate performance requirements into upper bounds on the complementary filters as explained in Section ref:ssec:detail_control_cf_trans_perf.
 4. Design the weighting functions $w_H$ and $w_L$ and generate the complementary filters using $\mathcal{H}_{\infty}\text{-synthesis}$ as described in Section ref:ssec:detail_control_sensor_hinf_method.
    If the synthesis fails to produce filters satisfying the defined upper bounds, either revise the requirements or develop a more accurate model $G$ that will allow for a smaller $w_I$.
    For simpler cases, the analytical formulas for complementary filters presented in Section ref:ssec:detail_control_cf_analytical_complementary_filters can be employed.
 5. If $K(s) = H_H^{-1}(s) G^{-1}(s)$ is not proper, add low-pass filters with sufficiently high corner frequencies to ensure realizability.
 
-**** Plant                                                         :ignore:
+**** Plant
 
 To evaluate this control architecture, a simple test model representative of many synchrotron positioning stages is utilized (Figure ref:fig:detail_control_cf_test_model).
 In this model, a payload with mass $m$ is positioned on top of a stage.
@@ -3794,11 +3823,13 @@ The positioning stage itself is characterized by stiffness $k$, internal damping
 The model of the plant $G(s)$ from actuator force $F$ to displacement $y$ is described by Equation eqref:eq:detail_control_cf_test_plant_tf.
 
 \begin{equation}\label{eq:detail_control_cf_test_plant_tf}
-  G(s) = \frac{1}{m s^2 + c s + k}, \quad m = \SI{20}{\kg},\ k = 1\si{\N/\mu\m},\ c = 10^2\si{\N\per(\m\per\s)}
+  G(s) = \frac{1}{m s^2 + c s + k}
 \end{equation}
 
-The plant dynamics include uncertainties related to limited support compliance, unmodeled flexible dynamics and payload dynamics.
+The parameter values are set to $m = \SI{20}{\kg}$, $k = 1\si{\N/\mu\m}$, and $c = 10^2\si{\N\per(\m\per\s)}$.
-These uncertainties are represented using a multiplicative input uncertainty weight eqref:eq:detail_control_cf_test_plant_uncertainty, which specifies the magnitude of uncertainty as a function of frequency.
+
+The plant dynamics include uncertainties related to limited support compliance, unmodeled flexible dynamics, payload dynamics, and other factors.
+These uncertainties are represented using a multiplicative input uncertainty weight eqref:eq:detail_control_cf_test_plant_uncertainty., which specifies the magnitude of uncertainty as a function of frequency:
 
 \begin{equation}\label{eq:detail_control_cf_test_plant_uncertainty}
   w_I(s) = 10 \cdot \frac{(s+100)^2}{(s+1000)^2}
@@ -3877,9 +3908,9 @@ exportFig('figs/detail_control_cf_bode_plot_mech_sys.pdf', 'width', 'half', 'hei
 
 **** Requirements and choice of complementary filters
 
-As discussed in Section ref:ssec:detail_control_cf_trans_perf, nominal performance requirements can be expressed as upper bounds on the shape of the complementary filters.
+As discussed in Section ref:ssec:detail_control_cf_trans_perf, nominal performance requirements can be expressed as upper bounds on the shapes of the complementary filters.
 For this example, the requirements are:
-- track ramp inputs (i.e. constant velocity scans) with zero steady-state error: a $+2$ slope at low frequencies for the magnitude of the sensitivity function $|S(j\omega)|$ is required
+- to track ramp inputs (constant velocity scans) with zero steady-state error, which necessitates a $+2$ slope at low frequencies for the magnitude of the sensitivity function $|S(j\omega)|$
 - filtering of measurement noise above $\SI{300}{Hz}$, where sensor noise is significant (requiring a filtering factor of approximately 100 above this frequency)
 - maximizing disturbance rejection
 
@@ -3889,9 +3920,8 @@ This condition is satisfied when the magnitude of the low-pass complementary fil
 Robust performance is achieved when both nominal performance and robust stability conditions are simultaneously satisfied.
 
 All requirements imposed on $H_L$ and $H_H$ are visualized in Figure ref:fig:detail_control_cf_specs_S_T.
-While $\mathcal{H}_\infty\text{-synthesis}$ could be employed to design the complementary filters, analytical formulas were used for this relatively simple example.
+While $\mathcal{H}_\infty$ synthesis could be employed to design the complementary filters, analytical formulas were used for this relatively simple example.
-The second-order complementary filters from Equation eqref:eq:detail_control_cf_2nd_order were selected with parameters $\alpha = 1$ and $\omega_0 = 2\pi \cdot 20\,\text{Hz}$.
+Specifically, the second-order complementary filters from Equation eqref:eq:detail_control_cf_2nd_order were selected, providing the desired $+2$ and $-2$ slopes, with parameters $\alpha = 1$ and $\omega_0 = 2\pi \cdot 20$ Hz.
-There magnitudes are displayed in Figure ref:fig:detail_control_cf_specs_S_T, confirming that these complementary filters are fulfilling the specifications.
 
 #+name: fig:detail_control_cf_specs_S_T_obtained_filters
 #+caption: Performance requirement and complementary filters used (\subref{fig:detail_control_cf_specs_S_T}). Obtained controller from the complementary filters and the plant inverse is shown in (\subref{fig:detail_control_cf_bode_Kfb}).
@@ -4128,7 +4158,7 @@ In this section, a control architecture in which complementary filters are used
 This approach differs from traditional open-loop shaping in that no controller is manually designed; rather, appropriate complementary filters are selected to achieve the desired closed-loop behavior.
 The method shares conceptual similarities with mixed-sensitivity $\mathcal{H}_{\infty}\text{-synthesis}$, as both approaches aim to shape closed-loop transfer functions, but with notable distinctions in implementation and complexity.
 
-While $\mathcal{H}_{\infty}\text{-synthesis}$ offers greater flexibility and can be readily generalized to MIMO plants, the presented approach provides a simpler alternative that requires minimal design effort.
+While $\mathcal{H}_{\infty}\text{-synthesis}$ synthesis offers greater flexibility and can be readily generalized to MIMO plants, the presented approach provides a simpler alternative that requires minimal design effort.
 Implementation only necessitates extracting a model of the plant and selecting appropriate analytical complementary filters, making it particularly interesting for applications where simplicity and intuitive parameter tuning are valued.
 
 Due to time constraints, an extensive literature review comparing this approach with similar existing architectures, such as Internal Model Control [[cite:&saxena12_advan_inter_model_contr_techn]], was not conducted.
@@ -4143,21 +4173,6 @@ It will be experimentally validated with the NASS during the experimental phase.
 :END:
 <<sec:detail_control_conclusion>>
 
-In order to optimize the control of the Nano Active Stabilization System, several aspects of control theory were studied.
-Different approaches to combine sensors were compared in Section ref:sec:detail_control_sensor.
-While High Authority Control-Low Authority Control (HAC-LAC) was successfully applied during the conceptual design phase, the focus of this work was extended to sensor fusion techniques where two or more sensors are combined using complementary filters.
-It was demonstrated that the performance of such fusion depends significantly on the magnitude of the complementary filters.
-To address this challenge, a synthesis method based on $\mathcal{H}_\infty\text{-synthesis}$ was proposed, allowing for intuitive shaping of the complementary filters through weighting functions.
-For the NASS, while HAC-LAC remains a natural way to combine sensors, the potential benefits of sensor fusion merit further investigation.
-
-Various decoupling strategies for parallel manipulators were examined in Section ref:sec:detail_control_decoupling, including decentralized control, Jacobian decoupling, modal decoupling, and Singular Value Decomposition (SVD) decoupling.
-The main characteristics of each approach were highlighted, providing valuable insights into their respective strengths and limitations.
-Among the examined methods, Jacobian decoupling was determined to be most appropriate for the NASS, as it provides straightforward implementation while preserving the physical meaning of inputs and outputs.
-
-With the system successfully decoupled, attention shifted to designing appropriate SISO controllers for each decoupled direction.
-A control architecture for directly shaping closed-loop transfer functions was proposed.
-It is based on complementary filters that can be designed using either the proposed $\mathcal{H}_\infty\text{-synthesis}$ approach described earlier or through analytical formulas.
-Experimental validation of this method on the NASS will be conducted during the experimental tests on ID31.
 
 * Bibliography                                                        :ignore:
 #+latex: \printbibliography[heading=bibintoc,title={Bibliography}]

nass-control.tex

@@ -1,4 +1,4 @@
-% Created 2025-04-13 Sun 17:08
+% Created 2025-04-11 Fri 14:30
 % Intended LaTeX compiler: pdflatex
 \documentclass[a4paper, 10pt, DIV=12, parskip=full, bibliography=totoc]{scrreprt}
 
@@ -23,29 +23,32 @@
 \tableofcontents
 
 \clearpage
-Three critical elements for the control of parallel manipulators such as the Nano-Hexapod were identified: effective utilization and combination of multiple sensors, appropriate plant decoupling strategies, and robust controller design for the decoupled system.
+When controlling a MIMO system (specifically parallel manipulator such as the Stewart platform?)
 
-During the conceptual design phase of the NASS, pragmatic approaches were implemented for each of these elements.
+\begin{itemize}
-The High Authority Control-Low Authority Control (HAC-LAC) architecture was selected for combining sensors.
+\item[{$\square$}] \textbf{Should the quick review of Stewart platform control be here?}
-Control was implemented in the frame of the struts, leveraging the inherent low-frequency decoupling of the plant where all decoupled elements exhibited similar dynamics, thereby simplifying the Single-Input Single-Output (SISO) controller design process.
+In that case it should be possible to highlight three areas:
-For these decoupled plants, open-loop shaping techniques were employed to tune the individual controllers.
+\begin{itemize}
+\item use of multiple sensors
+\item decoupling strategy
+\item control optimization
+\end{itemize}
+\end{itemize}
 
-While these initial strategies proved effective in validating the NASS concept, this work explores alternative approaches with the potential to further enhance the performance.
+Several considerations:
-Section \ref{sec:detail_control_sensor} examines different methods for combining multiple sensors, with particular emphasis on sensor fusion techniques that utilize complementary filters.
+\begin{itemize}
-A novel approach for designing these filters is proposed, which allows optimization of the sensor fusion effectiveness.
+\item Section \ref{sec:detail_control_sensor}: How to most effectively use/combine multiple sensors
-
+\item Section \ref{sec:detail_control_decoupling}: How to decouple a system
-Section \ref{sec:detail_control_decoupling} presents a comparative analysis of various decoupling strategies, including Jacobian decoupling, modal decoupling, and Singular Value Decomposition (SVD) decoupling.
+\item Section \ref{sec:detail_control_cf}: How to design the controller
-Each method is evaluated in terms of its theoretical foundations, implementation requirements, and performance characteristics, providing insights into their respective advantages for different applications.
+\end{itemize}
-
-Finally, Section \ref{sec:detail_control_cf} addresses the challenge of controller design for decoupled plants.
-A method for directly shaping closed-loop transfer functions using complementary filters is proposed, offering an intuitive approach to achieving desired performance specifications while ensuring robustness to plant uncertainty.
 \chapter{Multiple Sensor Control}
 \label{sec:detail_control_sensor}
 
 The literature review of Stewart platforms revealed a wide diversity of designs with various sensor and actuator configurations.
-Control objectives (such as active damping, vibration isolation, or precise positioning) directly dictate sensor selection, whether inertial, force, or relative position sensors.
+Control objectives (such as active damping, vibration isolation, or precise positioning) dictate specific sensor configurations.
+The selection between inertial sensors, force sensors, or relative position sensors is primarily determined by the system's control requirements.
 
-In cases where multiple control objectives must be achieved simultaneously, as is the case for the Nano Active Stabilization System (NASS) where the Stewart platform must both position the sample and provide isolation from micro-station vibrations, combining multiple sensors within the control architecture has been demonstrated to yield significant performance benefits \cite{hauge04_sensor_contr_space_based_six}.
+In cases where multiple control objectives must be achieved simultaneously, as is the case for the Nano Active Stabilization System (NASS) where the Stewart platform must both position the sample and provide isolation from micro-station vibrations, combining multiple sensors within the control architecture has been demonstrated to yield significant performance benefits.
 From the literature, three principal approaches for combining sensors have been identified: High Authority Control-Low Authority Control (HAC-LAC), sensor fusion, and two-sensor control architectures.
 
 \begin{figure}[htbp]
@@ -72,7 +75,7 @@ From the literature, three principal approaches for combining sensors have been
 \caption{\label{fig:detail_control_control_multiple_sensors}Different control strategies when using multiple sensors. High Authority Control / Low Authority Control (\subref{fig:detail_control_sensor_arch_hac_lac}). Sensor Fusion (\subref{fig:detail_control_sensor_arch_sensor_fusion}). Two-Sensor Control (\subref{fig:detail_control_sensor_arch_two_sensor_control})}
 \end{figure}
 
-The HAC-LAC approach employs a dual-loop control strategy in which two control loops utilize different sensors for distinct purposes (Figure \ref{fig:detail_control_sensor_arch_hac_lac}).
+The HAC-LAC approach, implemented during the conceptual phase, employs a dual-loop control strategy in which two control loops utilize different sensors for distinct purposes (Figure \ref{fig:detail_control_sensor_arch_hac_lac}).
 In \cite{li01_simul_vibrat_isolat_point_contr}, vibration isolation is provided by accelerometers collocated with the voice coil actuators, while external rotational sensors are utilized to achieve pointing control.
 In \cite{geng95_intel_contr_system_multip_degree}, force sensors collocated with the magnetostrictive actuators are used for active damping using decentralized IFF, and subsequently accelerometers are employed for adaptive vibration isolation.
 Similarly, in \cite{wang16_inves_activ_vibrat_isolat_stewar}, piezoelectric actuators with collocated force sensors are used in a decentralized manner to provide active damping while accelerometers are implemented in an adaptive feedback loop to suppress periodic vibrations.
@@ -80,7 +83,7 @@ In \cite{xie17_model_contr_hybrid_passiv_activ}, force sensors are integrated in
 
 The second approach, sensor fusion (illustrated in Figure \ref{fig:detail_control_sensor_arch_sensor_fusion}), involves filtering signals from two sensors using complementary filters\footnote{A set of two complementary filters are two transfer functions that sum to one.} and summing them to create an improved sensor signal.
 In \cite{hauge04_sensor_contr_space_based_six}, geophones (used at low frequency) are merged with force sensors (used at high frequency).
-It is demonstrated that combining both sensors using sensor fusion can improve performance compared to using only one of the two sensors.
+It is demonstrated that combining both sensors using sensor fusion can improve performance compared to using the individual sensors independently.
 In \cite{tjepkema12_sensor_fusion_activ_vibrat_isolat_precis_equip}, sensor fusion architecture is implemented with an accelerometer and a force sensor.
 This implementation is shown to simultaneously achieve high damping of structural modes (through the force sensors) while maintaining very low vibration transmissibility (through the accelerometers).
 
@@ -93,20 +96,25 @@ A ``two-sensor control'' approach was proven to perform better than controllers
 A Linear Quadratic Regulator (LQG) was employed to optimize the two-input/one-output controller.
 
 Beyond these three main approaches, other control architectures have been proposed for different purposes.
-For instance, in \cite{yang19_dynam_model_decoup_contr_flexib}, a first control loop utilizes force sensors and relative motion sensors to compensate for parasitic stiffness of the flexible joints.
+In \cite{yang19_dynam_model_decoup_contr_flexib}, a first control loop utilizes force sensors and relative motion sensors to compensate for parasitic stiffness of the flexible joints.
 Subsequently, the system is decoupled in the modal space (facilitated by the removal of parasitic stiffness) and accelerometers are employed for vibration isolation.
 
 The HAC-LAC architecture was previously investigated during the conceptual phase and successfully implemented to validate the NASS concept, demonstrating excellent performance.
 At the other end of the spectrum, the two-sensor approach yields greater control design freedom but introduces increased complexity in tuning, and thus was not pursued in this study.
 This work instead focuses on sensor fusion, which represents a promising middle ground between the proven HAC-LAC approach and the more complex two-sensor control strategy.
 
-A review of sensor fusion is first presented in Section \ref{ssec:detail_control_sensor_review}.
+A review of sensor fusion is first presented (Section \ref{ssec:detail_control_sensor_review}), followed by an examination of the fundamental theoretical concepts (Section \ref{ssec:detail_control_sensor_fusion_requirements}).
-Then, in Section \ref{ssec:detail_control_sensor_fusion_requirements}, both the robustness of the fusion and the noise characteristics of the resulting ``fused sensor'' are derived and expressed as functions of the complementary filters' norms.
+In this section, both the robustness of the fusion and the noise characteristics of the resulting ``super sensor'' are derived and expressed as functions of the complementary filters' norms.
-A synthesis method for shaping complementary filters is proposed in Section \ref{ssec:detail_control_sensor_hinf_method}.
+A synthesis method for designing complementary filters that allow to shape their norms is proposed (Section \ref{ssec:detail_control_sensor_hinf_method}).
 The investigation is then extended beyond the conventional two-sensor scenario, demonstrating how the proposed complementary filter synthesis can be generalized for applications requiring the fusion of three or more sensors (Section \ref{ssec:detail_control_sensor_hinf_three_comp_filters}).
 \section{Review of Sensor Fusion}
 \label{ssec:detail_control_sensor_review}
 
+Sensors used to measure physical quantities have two primary limitations: measurement accuracy which is compromised by various noise sources (including electrical noise from conditioning electronics), and limited measurement bandwidth.
+Sensor fusion offers a solution to these limitations by combining multiple sensors \cite{bendat57_optim_filter_indep_measur_two}.
+By strategically selecting sensors with complementary characteristics, a ``super sensor'' can be created that combines the advantages of each individual sensor.
+
+
 Measuring a physical quantity using sensors is always subject to several limitations.
 First, the accuracy of the measurement is affected by various noise sources, such as electrical noise from the conditioning electronics.
 Second, the frequency range in which the measurement is relevant is bounded by the bandwidth of the sensor.
@@ -120,7 +128,7 @@ In other applications, sensor fusion is utilized to obtain an estimate of the me
 More recently, the fusion of sensors measuring different physical quantities has been proposed to enhance control properties \cite{collette15_sensor_fusion_method_high_perfor,yong16_high_speed_vertic_posit_stage}.
 In \cite{collette15_sensor_fusion_method_high_perfor}, an inertial sensor used for active vibration isolation is fused with a sensor collocated with the actuator to improve the stability margins of the feedback controller.
 
-Beyond Stewart platforms, practical applications of sensor fusion are numerous.
+On top of Stewart platforms, practical applications of sensor fusion are numerous.
 It is widely implemented for attitude estimation in autonomous vehicles such as unmanned aerial vehicles \cite{baerveldt97_low_cost_low_weigh_attit,corke04_inert_visual_sensin_system_small_auton_helic,jensen13_basic_uas} and underwater vehicles \cite{pascoal99_navig_system_desig_using_time,batista10_optim_posit_veloc_navig_filter_auton_vehic}.
 Sensor fusion offers significant benefits for high-performance positioning control as demonstrated in \cite{shaw90_bandw_enhan_posit_measur_using_measur_accel,zimmermann92_high_bandw_orien_measur_contr,min15_compl_filter_desig_angle_estim,yong16_high_speed_vertic_posit_stage}.
 It has also been identified as a key technology for improving the performance of active vibration isolation systems \cite{tjepkema12_sensor_fusion_activ_vibrat_isolat_precis_equip}.
@@ -136,10 +144,14 @@ In early implementations of complementary filtering, analog circuits were used t
 While analog complementary filters remain in use today \cite{yong16_high_speed_vertic_posit_stage,moore19_capac_instr_sensor_fusion_high_bandw_nanop}, digital implementation is now more common as it provides greater flexibility.
 
 Various design methods have been developed to optimize complementary filters.
-The most straightforward approach utilizes analytical formulas, which depending on the application may be first order \cite{corke04_inert_visual_sensin_system_small_auton_helic,yeh05_model_contr_hydraul_actuat_two,yong16_high_speed_vertic_posit_stage}, second order \cite{baerveldt97_low_cost_low_weigh_attit,stoten01_fusion_kinet_data_using_compos_filter,jensen13_basic_uas}, or higher orders \cite{shaw90_bandw_enhan_posit_measur_using_measur_accel,zimmermann92_high_bandw_orien_measur_contr,stoten01_fusion_kinet_data_using_compos_filter,collette15_sensor_fusion_method_high_perfor,matichard15_seism_isolat_advan_ligo}.
+The most straightforward approach utilizes analytical formulas.
-Since the characteristics of the super sensor depend on proper complementary filter design \cite{dehaeze19_compl_filter_shapin_using_synth}, several optimization techniques have emerged—ranging from optimizing parameters for analytical formulas \cite{jensen13_basic_uas,min15_compl_filter_desig_angle_estim,fonseca15_compl} to employing convex optimization tools \cite{hua04_polyp_fir_compl_filter_contr_system,hua05_low_ligo} such as linear matrix inequalities \cite{pascoal99_navig_system_desig_using_time}.
+Depending on the application, these formulas may be of first order \cite{corke04_inert_visual_sensin_system_small_auton_helic,yeh05_model_contr_hydraul_actuat_two,yong16_high_speed_vertic_posit_stage}, second order \cite{baerveldt97_low_cost_low_weigh_attit,stoten01_fusion_kinet_data_using_compos_filter,jensen13_basic_uas}, or higher orders \cite{shaw90_bandw_enhan_posit_measur_using_measur_accel,zimmermann92_high_bandw_orien_measur_contr,stoten01_fusion_kinet_data_using_compos_filter,collette15_sensor_fusion_method_high_perfor,matichard15_seism_isolat_advan_ligo}.
-As demonstrated in \cite{plummer06_optim_compl_filter_their_applic_motion_measur}, complementary filter design can be linked to the standard mixed-sensitivity control problem, allowing powerful classical control theory tools to be applied.
+
-For example, in \cite{jensen13_basic_uas}, two gains of a Proportional Integral (PI) controller are optimized to minimize super sensor noise.
+Since the characteristics of the super sensor depend on the proper design of complementary filters \cite{dehaeze19_compl_filter_shapin_using_synth}, several optimization techniques have been developed.
+Some approaches focus on finding optimal parameters for analytical formulas \cite{jensen13_basic_uas,min15_compl_filter_desig_angle_estim,fonseca15_compl}, while others employ convex optimization tools \cite{hua04_polyp_fir_compl_filter_contr_system,hua05_low_ligo} such as linear matrix inequalities \cite{pascoal99_navig_system_desig_using_time}.
+As demonstrated in \cite{plummer06_optim_compl_filter_their_applic_motion_measur}, complementary filter design can be linked to the standard mixed-sensitivity control problem.
+Consequently, the powerful tools developed for classical control theory can be applied to complementary filter design.
+For example, in \cite{jensen13_basic_uas}, the two gains of a Proportional Integral (PI) controller are optimized to minimize super sensor noise.
 
 All these complementary filter design methods share the common objective of creating a super sensor with desired characteristics, typically in terms of noise and dynamics.
 As reported in \cite{zimmermann92_high_bandw_orien_measur_contr,plummer06_optim_compl_filter_their_applic_motion_measur}, phase shifts and magnitude bumps in the super sensor dynamics may occur if complementary filters are poorly designed or if sensors are improperly calibrated.
@@ -147,7 +159,7 @@ Therefore, the robustness of the fusion must be considered when designing comple
 Despite the numerous design methods proposed in the literature, a simple approach that specifies desired super sensor characteristics while ensuring good fusion robustness has been lacking.
 
 Fortunately, both fusion robustness and super sensor characteristics can be linked to complementary filter magnitude \cite{dehaeze19_compl_filter_shapin_using_synth}.
-Based on this relationship, the present work introduces an approach to designing complementary filters using \(\mathcal{H}_\infty\text{-synthesis}\), which enables intuitive shaping of complementary filter magnitude in a straightforward manner.
+Based on this relationship, the present work introduces an approach to designing complementary filters using \(\mathcal{H}_\infty\) synthesis, which enables intuitive shaping of complementary filter magnitude in a straightforward manner.
 \section{Sensor Fusion and Complementary Filters Requirements}
 \label{ssec:detail_control_sensor_fusion_requirements}
 A general sensor fusion architecture using complementary filters is shown in Figure \ref{fig:detail_control_sensor_fusion_overview}, where multiple sensors (in this case two) measure the same physical quantity \(x\).
@@ -219,7 +231,7 @@ The effects of imperfect normalization will be addressed subsequently.
 In that case, the super sensor output \(\hat{x}\) equals \(x\) plus the filtered noise from both sensors \eqref{eq:detail_control_sensor_estimate_perfect_dyn}.
 From this equation, it is evident that the complementary filters \(H_1(s)\) and \(H_2(s)\) operate solely on the sensor noise.
 Thus, this sensor fusion architecture allows filtering of sensor noise without introducing distortion in the measured physical quantity.
-This fundamental property necessitates that the two filters are complementary.
+This fundamental property necessitates that the two filters must be complementary.
 
 \begin{equation}\label{eq:detail_control_sensor_estimate_perfect_dyn}
   \hat{x} = x + H_1(s) n_1 + H_2(s) n_2
@@ -241,13 +253,15 @@ If the two sensors have identical noise characteristics (\(\Phi_{n_1}(\omega) =
 This represents the simplest form of sensor fusion using complementary filters.
 
 However, sensors typically exhibit high noise levels in different frequency regions.
-In such cases, to reduce the noise of the super sensor, \(|H_1(j\omega)|\) should be minimized when \(\Phi_{n_1}(\omega)\) exceeds \(\Phi_{n_2}(\omega)\), and \(|H_2(j\omega)|\) should be minimized when \(\Phi_{n_2}(\omega)\) exceeds \(\Phi_{n_1}(\omega)\).
+In such cases, to reduce the noise of the super sensor, the norm \(|H_1(j\omega)|\) should be minimized when \(\Phi_{n_1}(\omega)\) exceeds \(\Phi_{n_2}(\omega)\), and the norm \(|H_2(j\omega)|\) should be minimized when \(\Phi_{n_2}(\omega)\) exceeds \(\Phi_{n_1}(\omega)\).
 Therefore, by appropriately shaping the norm of the complementary filters, the noise of the super sensor can be minimized.
 \paragraph{Sensor Fusion Robustness}
 
 In practical systems, sensor normalization is rarely perfect, and condition \eqref{eq:detail_control_sensor_perfect_dynamics} is not fully satisfied.
+
 To analyze such imperfections, a multiplicative input uncertainty is incorporated into the sensor dynamics (Figure \ref{fig:detail_control_sensor_model_uncertainty}).
 The nominal model is the estimated model used for normalization \(\hat{G}_i(s)\), \(\Delta_i(s)\) is any stable transfer function satisfying \(|\Delta_i(j\omega)| \le 1,\ \forall\omega\), and \(w_i(s)\) is a weighting transfer function representing the magnitude of uncertainty.
+The weight \(w_i(s)\) is selected such that the actual sensor dynamics \(G_i(j\omega)\) remains within the uncertain region represented by a circle in the complex plane, centered on \(1\) with a radius equal to \(|w_i(j\omega)|\).
 
 Since the nominal sensor dynamics is taken as the normalized filter, the normalized sensor model can be further simplified as shown in Figure \ref{fig:detail_control_sensor_model_uncertainty_simplified}.
 
@@ -262,7 +276,7 @@ Since the nominal sensor dynamics is taken as the normalized filter, the normali
 \begin{center}
 \includegraphics[scale=1,width=0.95\linewidth]{figs/detail_control_sensor_model_uncertainty_simplified.png}
 \end{center}
-\subcaption{\label{fig:detail_control_sensor_model_uncertainty_simplified}Simplified normalized sensor model}
+\subcaption{\label{fig:detail_control_sensor_model_uncertainty_simplified}Simplified sensor model}
 \end{subfigure}
 \caption{\label{fig:detail_control_sensor_models_uncertainty}Sensor models with dynamical uncertainty}
 \end{figure}
@@ -271,6 +285,11 @@ The sensor fusion architecture incorporating sensor models with dynamical uncert
 The super sensor dynamics \eqref{eq:detail_control_sensor_super_sensor_dyn_uncertainty} is no longer unity but depends on the sensor dynamical uncertainty weights \(w_i(s)\) and the complementary filters \(H_i(s)\).
 The dynamical uncertainty of the super sensor can be graphically represented in the complex plane by a circle centered on \(1\) with a radius equal to \(|w_1(j\omega) H_1(j\omega)| + |w_2(j\omega) H_2(j\omega)|\) (Figure \ref{fig:detail_control_sensor_uncertainty_set_super_sensor}).
 
+
+The sensor fusion architecture with the sensor models including dynamical uncertainty is shown in Figure \ref{fig:detail_control_sensor_fusion_dynamic_uncertainty}.
+The super sensor dynamics \eqref{eq:detail_control_sensor_super_sensor_dyn_uncertainty} is no longer equal to \(1\) and now depends on the sensor dynamical uncertainty weights \(w_i(s)\) as well as on the complementary filters \(H_i(s)\).
+The dynamical uncertainty of the super sensor can be graphically represented in the complex plane by a circle centered on \(1\) with a radius equal to \(|w_1(j\omega) H_1(j\omega)| + |w_2(j\omega) H_2(j\omega)|\) (Figure \ref{fig:detail_control_sensor_uncertainty_set_super_sensor}).
+
 \begin{equation}\label{eq:detail_control_sensor_super_sensor_dyn_uncertainty}
   \frac{\hat{x}}{x} = 1 + w_1(s) H_1(s) \Delta_1(s) + w_2(s) H_2(s) \Delta_2(s)
 \end{equation}
@@ -298,7 +317,7 @@ As it is generally desired to limit the dynamical uncertainty of the super senso
 As established in Section \ref{ssec:detail_control_sensor_fusion_requirements}, the super sensor's noise characteristics and robustness are directly dependent on the complementary filters' norm.
 A synthesis method enabling precise shaping of these norms would therefore offer substantial practical benefits.
 This section develops such an approach by formulating the design objective as a standard \(\mathcal{H}_\infty\) optimization problem.
-The methodology for designing appropriate weighting functions (which specify desired complementary filter shape during synthesis) is examined in detail, and the efficacy of the proposed method is validated with a simple example.
+The methodology for designing appropriate weighting functions (which specify desired complementary filter shapes during synthesis) is examined in detail, and the efficacy of the proposed method is validated with a simple example.
 \paragraph{Synthesis Objective}
 
 The primary objective is to shape the norms of two filters \(H_1(s)\) and \(H_2(s)\) while ensuring they maintain their complementary property as defined in \eqref{eq:detail_control_sensor_comp_filter}.
@@ -314,7 +333,8 @@ Weighting transfer functions \(W_1(s)\) and \(W_2(s)\) are strategically selecte
 \end{subequations}
 \paragraph{Shaping of Complementary Filters using \(\mathcal{H}_\infty\) synthesis}
 
-The synthesis objective can be expressed as a standard \(\mathcal{H}_\infty\) optimization problem by considering the generalized plant \(P(s)\) illustrated in Figure \ref{fig:detail_control_sensor_h_infinity_robust_fusion_plant} and mathematically described by \eqref{eq:detail_control_sensor_generalized_plant}.
+The synthesis objective can be readily expressed as a standard \(\mathcal{H}_\infty\) optimization problem and solved using widely available computational tools.
+Consider the generalized plant \(P(s)\) illustrated in Figure \ref{fig:detail_control_sensor_h_infinity_robust_fusion_plant} and mathematically described by \eqref{eq:detail_control_sensor_generalized_plant}.
 
 \begin{equation}\label{eq:detail_control_sensor_generalized_plant}
   \begin{bmatrix} z_1 \\ z_2 \\ v \end{bmatrix} = P(s) \begin{bmatrix} w\\u \end{bmatrix}; \quad P(s) = \begin{bmatrix}W_1(s) & -W_1(s) \\ 0 & \phantom{+}W_2(s) \\  1 & 0 \end{bmatrix}
@@ -333,16 +353,16 @@ The synthesis objective can be expressed as a standard \(\mathcal{H}_\infty\) op
 \end{center}
 \subcaption{\label{fig:detail_control_sensor_h_infinity_robust_fusion_fb}Generalized plant with the synthesized filter}
 \end{subfigure}
-\caption{\label{fig:detail_control_sensor_h_infinity_robust_fusion}Architecture for the \(\mathcal{H}_\infty\text{-synthesis}\) of complementary filters}
+\caption{\label{fig:detail_control_sensor_h_infinity_robust_fusion}Architecture for the \(\mathcal{H}_\infty\) synthesis of complementary filters}
 \end{figure}
 
-Applying standard \(\mathcal{H}_\infty\text{-synthesis}\) to the generalized plant \(P(s)\) is equivalent to finding a stable filter \(H_2(s)\) that, based on input \(v\), generates an output signal \(u\) such that the \(\mathcal{H}_\infty\) norm of the system shown in Figure \ref{fig:detail_control_sensor_h_infinity_robust_fusion_fb} from \(w\) to \([z_1, \ z_2]\) does not exceed unity, as expressed in \eqref{eq:detail_control_sensor_hinf_syn_obj}.
+Applying standard \(\mathcal{H}_\infty\) synthesis to the generalized plant \(P(s)\) is equivalent to finding a stable filter \(H_2(s)\) that, based on input \(v\), generates an output signal \(u\) such that the \(\mathcal{H}_\infty\) norm of the system shown in Figure \ref{fig:detail_control_sensor_h_infinity_robust_fusion_fb} from \(w\) to \([z_1, \ z_2]\) does not exceed unity, as expressed in \eqref{eq:detail_control_sensor_hinf_syn_obj}.
 
 \begin{equation}\label{eq:detail_control_sensor_hinf_syn_obj}
   \left\|\begin{matrix} \left(1 - H_2(s)\right) W_1(s) \\ H_2(s) W_2(s) \end{matrix}\right\|_\infty \le 1
 \end{equation}
 
-By defining \(H_1(s)\) as the complement of \(H_2(s)\) \eqref{eq:detail_control_sensor_definition_H1}, the \(\mathcal{H}_\infty\text{-synthesis}\) objective becomes equivalent to \eqref{eq:detail_control_sensor_hinf_problem}, ensuring that conditions \eqref{eq:detail_control_sensor_hinf_cond_h1} and \eqref{eq:detail_control_sensor_hinf_cond_h2} are satisfied.
+By defining \(H_1(s)\) as the complement of \(H_2(s)\) (\eqref{eq:detail_control_sensor_definition_H1}), the \(\mathcal{H}_\infty\) synthesis objective becomes equivalent to \eqref{eq:detail_control_sensor_hinf_problem}, ensuring that conditions \eqref{eq:detail_control_sensor_hinf_cond_h1} and \eqref{eq:detail_control_sensor_hinf_cond_h2} are satisfied.
 
 \begin{equation}\label{eq:detail_control_sensor_definition_H1}
   H_1(s) \triangleq 1 - H_2(s)
@@ -352,19 +372,19 @@ By defining \(H_1(s)\) as the complement of \(H_2(s)\) \eqref{eq:detail_control_
   \left\|\begin{matrix} H_1(s) W_1(s) \\ H_2(s) W_2(s) \end{matrix}\right\|_\infty \le 1
 \end{equation}
 
-Therefore, applying \(\mathcal{H}_\infty\text{-synthesis}\) to the standard plant \(P(s)\) generates two filters, \(H_2(s)\) and \(H_1(s) \triangleq 1 - H_2(s)\), that are complementary as required by \eqref{eq:detail_control_sensor_comp_filter_problem_form}, with norms bounded by the specified constraints in \eqref{eq:detail_control_sensor_hinf_cond_h1} and \eqref{eq:detail_control_sensor_hinf_cond_h2}.
+Therefore, applying \(\mathcal{H}_\infty\) synthesis to the standard plant \(P(s)\) (\eqref{eq:detail_control_sensor_generalized_plant}) generates two filters, \(H_2(s)\) and \(H_1(s) \triangleq 1 - H_2(s)\), that are complementary as required by \eqref{eq:detail_control_sensor_comp_filter_problem_form}, with norms bounded by the specified constraints in \eqref{eq:detail_control_sensor_hinf_cond_h1} and \eqref{eq:detail_control_sensor_hinf_cond_h2}.
 
 It should be noted that there exists only an implication (not an equivalence) between the \(\mathcal{H}_\infty\) norm condition in \eqref{eq:detail_control_sensor_hinf_problem} and the initial synthesis objectives in \eqref{eq:detail_control_sensor_hinf_cond_h1} and \eqref{eq:detail_control_sensor_hinf_cond_h2}.
-Consequently, the optimization may be somewhat conservative with respect to the set of filters on which it operates \cite[,Chap. 2.8.3]{skogestad07_multiv_feedb_contr}.
+Consequently, the optimization may be somewhat conservative with respect to the set of filters on which it operates (see \cite[,Chap. 2.8.3]{skogestad07_multiv_feedb_contr}).
 \paragraph{Weighting Functions Design}
 
 Weighting functions play a crucial role during synthesis by specifying the maximum allowable norms for the complementary filters.
-The proper design of these weighting functions is essential for the successful implementation of the proposed \(\mathcal{H}_\infty\text{-synthesis}\) approach.
+The proper design of these weighting functions is essential for the successful implementation of the proposed \(\mathcal{H}_\infty\) synthesis approach.
 
 Three key considerations should guide the design of weighting functions.
 First, only proper and stable transfer functions should be employed.
 Second, the order of the weighting functions should remain reasonably small to minimize computational costs associated with solving the optimization problem and to facilitate practical implementation of the filters (as the order of the synthesized filters equals the sum of the weighting functions' orders).
-Third, the fundamental limitations imposed by the complementary property \eqref{eq:detail_control_sensor_comp_filter} must be respected, which implies that \(|H_1(j\omega)|\) and \(|H_2(j\omega)|\) cannot both be made small at the same frequency.
+Third, the fundamental limitations imposed by the complementary property (\eqref{eq:detail_control_sensor_comp_filter}) must be respected, which implies that \(|H_1(j\omega)|\) and \(|H_2(j\omega)|\) cannot both be made small at the same frequency.
 
 When designing complementary filters, it is typically desirable to specify their slopes, ``blending'' frequency, and maximum gains at low and high frequencies.
 To facilitate the expression of these specifications, formula \eqref{eq:detail_control_sensor_weight_formula} is proposed for the design of weighting functions.
@@ -426,7 +446,7 @@ Parameter & \(W_1(s)\) & \(W_2(s)\)\\
 \end{center}
 \end{minipage}
 
-Standard \(\mathcal{H}_\infty\text{-synthesis}\) is then applied to the generalized plant shown in Figure \ref{fig:detail_control_sensor_h_infinity_robust_fusion_plant}.
+Standard \(\mathcal{H}_\infty\) synthesis is then applied to the generalized plant shown in Figure \ref{fig:detail_control_sensor_h_infinity_robust_fusion_plant}.
 This yields the filter \(H_2(s)\) that minimizes the \(\mathcal{H}_\infty\) norm from input \(w\) to outputs \([z_1,\ z_2]^{\intercal}\).
 The resulting \(\mathcal{H}_\infty\) norm is found to be close to unity, indicating successful synthesis: the norms of the complementary filters remain below the specified upper bounds.
 This is confirmed by the Bode plots of the obtained complementary filters in Figure \ref{fig:detail_control_sensor_hinf_filters_results}.
@@ -472,7 +492,7 @@ The synthesis objective is to compute a set of \(n\) stable transfer functions \
 The transfer functions \([W_1(s),\ W_2(s),\ \dots,\ W_n(s)]\) are weights selected to specify the maximum complementary filters' norm during synthesis.
 
 This synthesis objective is closely related to the one described in Section \ref{ssec:detail_control_sensor_hinf_method}, and the proposed synthesis method represents a generalization of the approach previously presented.
-A set of \(n\) complementary filters can be shaped by applying standard \(\mathcal{H}_\infty\text{-synthesis}\) to the generalized plant \(P_n(s)\) described by \eqref{eq:detail_control_sensor_generalized_plant_n_filters}.
+A set of \(n\) complementary filters can be shaped by applying standard \(\mathcal{H}_\infty\) synthesis to the generalized plant \(P_n(s)\) described by \eqref{eq:detail_control_sensor_generalized_plant_n_filters}.
 
 \begin{equation}\label{eq:detail_control_sensor_generalized_plant_n_filters}
   \begin{bmatrix} z_1 \\ \vdots \\ z_n \\ v \end{bmatrix} = P_n(s) \begin{bmatrix} w \\ u_1 \\ \vdots \\ u_{n-1} \end{bmatrix}; \quad
@@ -512,7 +532,7 @@ Consider the generalized plant \(P_3(s)\) shown in Figure \ref{fig:detail_contro
 \begin{figure}[htbp]
 \begin{subfigure}{0.48\textwidth}
 \begin{center}
-\includegraphics[scale=1,scale=0.9]{figs/detail_control_sensor_comp_filter_three_hinf_fb.png}
+\includegraphics[scale=1,width=0.95\linewidth]{figs/detail_control_sensor_comp_filter_three_hinf_fb.png}
 \end{center}
 \subcaption{\label{fig:detail_control_sensor_comp_filter_three_hinf_fb}Generalized plant with the synthesized filter}
 \end{subfigure}
@@ -522,10 +542,10 @@ Consider the generalized plant \(P_3(s)\) shown in Figure \ref{fig:detail_contro
 \end{center}
 \subcaption{\label{fig:detail_control_sensor_three_complementary_filters_results}Weights and obtained filters}
 \end{subfigure}
-\caption{\label{fig:detail_control_sensor_comp_filter_three_hinf}Architecture for the \(\mathcal{H}_\infty\text{-synthesis}\) of three complementary filters (\subref{fig:detail_control_sensor_comp_filter_three_hinf_fb}). Bode plot of the inverse weighting functions and of the three obtained complementary filters (\subref{fig:detail_control_sensor_three_complementary_filters_results})}
+\caption{\label{fig:detail_control_sensor_comp_filter_three_hinf}Architecture for the \(\mathcal{H}_\infty\) synthesis of three complementary filters (\subref{fig:detail_control_sensor_comp_filter_three_hinf_fb}). Bode plot of the inverse weighting functions and of the three obtained complementary filters (\subref{fig:detail_control_sensor_three_complementary_filters_results})}
 \end{figure}
 
-Standard \(\mathcal{H}_\infty\text{-synthesis}\) is performed on the generalized plant \(P_3(s)\).
+Standard \(\mathcal{H}_\infty\) synthesis is performed on the generalized plant \(P_3(s)\).
 Two filters, \(H_2(s)\) and \(H_3(s)\), are obtained such that the \(\mathcal{H}_\infty\) norm of the closed-loop transfer from \(w\) to \([z_1,\ z_2,\ z_3]\) of the system in Figure \ref{fig:detail_control_sensor_comp_filter_three_hinf_fb} is less than one.
 Filter \(H_1(s)\) is defined using \eqref{eq:detail_control_sensor_h1_compl_h2_h3}, thus ensuring the complementary property of the obtained set of filters.
 
@@ -535,17 +555,17 @@ Filter \(H_1(s)\) is defined using \eqref{eq:detail_control_sensor_h1_compl_h2_h
 
 Figure \ref{fig:detail_control_sensor_three_complementary_filters_results} displays the three synthesized complementary filters (solid lines), confirming the successful synthesis.
 \section*{Conclusion}
-A new method for designing complementary filters using the \(\mathcal{H}_\infty\text{-synthesis}\) has been proposed.
+A new method for designing complementary filters using the \(\mathcal{H}_\infty\) synthesis has been proposed.
 This approach allows shaping of the filter magnitudes through the use of weighting functions during synthesis.
 This capability is particularly valuable in practice since the characteristics of the super sensor are directly linked to the complementary filters' magnitude.
 Consequently, typical sensor fusion objectives can be effectively translated into requirements on the magnitudes of the filters.
 
-For the NASS, the HAC-LAC strategy was found to perform well and to offer the advantages of being both intuitive to understand and straightforward to tune.
+For the Nano Active Stabilization System (NASS), the High Authority Control-Integral Force Feedback (HAC-IFF) strategy was found to perform well and to offer the advantages of being both intuitive to understand and straightforward to tune.
-Looking forward, it would be interesting to investigate how sensor fusion (particularly between the force sensors and external metrology) compares to the HAC-IFF approach in terms of performance and robustness.
+Looking forward, it would be interesting to investigate how sensor fusion (particularly between the force sensor and external metrology) compares to the HAC-IFF approach in terms of performance and robustness.
 \chapter{Decoupling}
 \label{sec:detail_control_decoupling}
 
-The control of parallel manipulators (and any MIMO system in general) typically involves a two-step approach: first decoupling the plant dynamics (using various strategies discussed in this section), followed by the application of SISO control for the decoupled plant (discussed in section \ref{sec:detail_control_cf}).
+The control of parallel manipulators (and any MIMO system in general) typically involves a two-step approach: first decoupling the plant dynamics using various strategies, which will be discussed in this section, followed by the application of SISO control for the decoupled plant (discussed in section \ref{sec:detail_control_cf}).
 
 When sensors are integrated within the struts, decentralized control may be applied, as the system is already well decoupled at low frequency.
 For instance, \cite{furutani04_nanom_cuttin_machin_using_stewar} implemented a system where each strut consists of piezoelectric stack actuators and eddy current displacement sensors, with separate PI controllers for each strut.
@@ -557,24 +577,23 @@ This approach enables the implementation of controllers in a defined frame.
 It has been applied with various sensor types including force sensors \cite{mcinroy00_desig_contr_flexur_joint_hexap}, relative displacement sensors \cite{kim00_robus_track_contr_desig_dof_paral_manip}, and inertial sensors \cite{li01_simul_vibrat_isolat_point_contr,abbas14_vibrat_stewar_platf}.
 The Cartesian frame in which the system is decoupled is typically chosen at the point of interest (i.e., where the motion is of interest) or at the center of mass.
 
-Modal decoupling represents another noteworthy decoupling strategy, wherein the ``local'' plant inputs and outputs are mapped to the modal space.
+Modal control represents another noteworthy decoupling strategy, wherein the ``local'' plant inputs and outputs are mapped to the modal space.
 In this approach, multiple SISO plants, each corresponding to a single mode, can be controlled independently.
 This decoupling strategy has been implemented for active damping applications \cite{holterman05_activ_dampin_based_decoup_colloc_contr}, which is logical as it is often desirable to dampen specific modes.
 The strategy has also been employed in \cite{pu11_six_degree_of_freed_activ} for vibration isolation purposes using geophones, and in \cite{yang19_dynam_model_decoup_contr_flexib} using force sensors.
 
-Another completely different strategy would be to implement a multivariable control directly on the coupled system.
+Another completely different strategy, is to use implement a multivariable control directly on the coupled system.
 \(\mathcal{H}_\infty\) and \(\mu\text{-synthesis}\) were applied to a Stewart platform model in \cite{lei08_multi_objec_robus_activ_vibrat}.
-In \cite{xie17_model_contr_hybrid_passiv_activ}, decentralized force feedback was first applied, followed by \(\mathcal{H}_2\text{-synthesis}\) for vibration isolation based on accelerometers.
+In \cite{xie17_model_contr_hybrid_passiv_activ}, decentralized force feedback was first applied, followed by \(\mathcal{H}_2\) synthesis for vibration isolation based on accelerometers.
-\(\mathcal{H}_\infty\text{-synthesis}\) was also employed in \cite{jiao18_dynam_model_exper_analy_stewar} for active damping based on accelerometers.
+\(\mathcal{H}_\infty\) synthesis was also employed in \cite{jiao18_dynam_model_exper_analy_stewar} for active damping based on accelerometers.
-A comparative study between \(\mathcal{H}_\infty\text{-synthesis}\) and decentralized control in the frame of the struts was performed in \cite{thayer02_six_axis_vibrat_isolat_system}.
+\cite{thayer02_six_axis_vibrat_isolat_system} compared \(\mathcal{H}_\infty\) synthesis with decentralized control in the frame of the struts.
 Their experimental closed-loop results indicated that the \(\mathcal{H}_\infty\) controller did not outperform the decentralized controller in the frame of the struts.
-These limitations were attributed to the model's poor ability to predict off-diagonal dynamics, which is crucial for \(\mathcal{H}_\infty\text{-synthesis}\).
+These limitations were attributed to the model's poor ability to predict off-diagonal dynamics, which is crucial for \(\mathcal{H}_\infty\) synthesis.
 
 The purpose of this section is to compare several methods for the decoupling of parallel manipulators, an analysis that appears to be lacking in the literature.
-A simplified parallel manipulator model is introduced in Section \ref{ssec:detail_control_decoupling_model} as a test case for evaluating decoupling strategies.
+The analysis begins in Section \ref{ssec:detail_control_decoupling_model} with the introduction of a simplified parallel manipulator model that serves as the foundation for evaluating various decoupling strategies.
-The decentralized plant (transfer functions from actuators to sensors integrated in the struts) is examined in Section \ref{ssec:detail_control_decoupling_decentralized}.
+Sections \ref{ssec:detail_control_decoupling_jacobian} through \ref{ssec:detail_control_decoupling_svd} systematically examine three distinct approaches: Jacobian matrix decoupling, modal decoupling, and Singular Value Decomposition (SVD) decoupling, respectively.
-Three approaches are investigated across subsequent sections: Jacobian matrix decoupling (Section \ref{ssec:detail_control_decoupling_jacobian}), modal decoupling (Section \ref{ssec:detail_control_decoupling_modal}), and Singular Value Decomposition (SVD) decoupling (Section \ref{ssec:detail_control_decoupling_svd}).
+The comparative assessment of these three methodologies, along with concluding observations, is provided in Section \ref{ssec:detail_control_decoupling_comp}.
-Finally, a comparative analysis with concluding observations is provided in Section \ref{ssec:detail_control_decoupling_comp}.
 \section{Test Model}
 \label{ssec:detail_control_decoupling_model}
 
@@ -674,7 +693,7 @@ The obtained transfer function from \(\bm{\mathcal{\tau}}\) to \(\bm{\mathcal{L}
   \frac{\bm{\mathcal{L}}}{\bm{\mathcal{\tau}}}(s) = \bm{G}_{\mathcal{L}}(s) = \left( \bm{J}_{\{M\}}^{-\intercal} \bm{M}_{\{M\}} \bm{J}_{\{M\}}^{-1} s^2 + \bm{\mathcal{C}} s + \bm{\mathcal{K}} \right)^{-1}
 \end{equation}
 
-At low frequencies, the plant converges to a diagonal constant matrix whose diagonal elements are equal to the actuator stiffnesses \eqref{eq:detail_control_decoupling_plant_decentralized_low_freq}.
+At low frequencies, the plant converges to a diagonal constant matrix whose diagonal elements are related to the actuator stiffnesses \eqref{eq:detail_control_decoupling_plant_decentralized_low_freq}.
 At high frequencies, the plant converges to the mass matrix mapped in the frame of the struts, which is generally highly non-diagonal.
 
 \begin{equation}\label{eq:detail_control_decoupling_plant_decentralized_low_freq}
@@ -694,7 +713,7 @@ Depending on the symmetry present in the system, certain diagonal elements may e
 \label{ssec:detail_control_decoupling_jacobian}
 \paragraph{Jacobian Matrix}
 
-The Jacobian matrix \(\bm{J}_{\{O\}}\) serves a dual purpose in the decoupling process: it converts strut velocity \(\dot{\mathcal{L}}\) to payload velocity and angular velocity \(\dot{\bm{\mathcal{X}}}_{\{O\}}\), and it transforms actuator forces \(\bm{\tau}\) to forces/torque applied on the payload \(\bm{\mathcal{F}}_{\{O\}}\), as expressed in equation \eqref{eq:detail_control_decoupling_jacobian}.
+The Jacobian matrix serves a dual purpose in the decoupling process: it converts strut velocity \(\dot{\mathcal{L}}\) to payload velocity and angular velocity \(\dot{\bm{\mathcal{X}}}_{\{O\}}\), and it transforms actuator forces \(\bm{\tau}\) to forces/torque applied on the payload \(\bm{\mathcal{F}}_{\{O\}}\), as expressed in equation \eqref{eq:detail_control_decoupling_jacobian}.
 
 \begin{subequations}\label{eq:detail_control_decoupling_jacobian}
   \begin{align}
@@ -799,7 +818,7 @@ However, it could alternatively be determined through analytical methods to ensu
 It should be noted that the existence of such a center of stiffness (i.e. a frame \(\{K\}\) for which \(\bm{J}_{\{K\}}^{\intercal} \bm{\mathcal{K}} \bm{J}_{\{K\}}\) is diagonal) is not guaranteed for arbitrary systems.
 This property is typically achievable only in systems exhibiting specific symmetrical characteristics, as is the case in the present example.
 
-The analytical expression for the plant in this configuration was then computed \eqref{eq:detail_control_decoupling_plant_CoK}.
+The analytical expression for the plant in this configuration was then computed \ref{eq:detail_control_decoupling_plant_CoK}.
 
 \begin{equation}\label{eq:detail_control_decoupling_plant_CoK}
   \frac{\bm{\mathcal{X}}_{\{K\}}}{\bm{\mathcal{F}}_{\{K\}}}(s) = \bm{G}_{\{K\}}(s) = \left( \bm{J}_{\{K\}}^{\intercal} \bm{J}_{\{M\}}^{-\intercal} \bm{M}_{\{M\}} \bm{J}_{\{M\}}^{-1} \bm{J}_{\{K\}} s^2 + \bm{J}_{\{K\}}^{\intercal} \bm{\mathcal{C}} \bm{J}_{\{K\}} s + \bm{J}_{\{K\}}^{\intercal} \bm{\mathcal{K}} \bm{J}_{\{K\}} \right)^{-1}
@@ -815,6 +834,7 @@ The plant is well decoupled below the suspension mode with the lowest frequency
 
 The physical reason for high-frequency coupling is illustrated in Figure \ref{fig:detail_control_decoupling_model_test_CoK}.
 When a high-frequency force is applied at a point not aligned with the center of mass, it induces rotation around the center of mass.
+This phenomenon explains the coupling observed between different degrees of freedom at higher frequencies.
 
 \begin{figure}[htbp]
 \begin{subfigure}{0.48\textwidth}
@@ -834,6 +854,7 @@ When a high-frequency force is applied at a point not aligned with the center of
 \section{Modal Decoupling}
 \label{ssec:detail_control_decoupling_modal}
 Modal decoupling represents an approach based on the principle that a mechanical system's behavior can be understood as a combination of contributions from various modes \cite{rankers98_machin}.
+
 To convert the dynamics in the modal space, the equation of motion are first written with respect to the center of mass \eqref{eq:detail_control_decoupling_equation_motion_CoM}.
 
 \begin{equation}\label{eq:detail_control_decoupling_equation_motion_CoM}
@@ -914,7 +935,7 @@ Each of these diagonal elements corresponds to a specific mode, as shown in Figu
 \label{ssec:detail_control_decoupling_svd}
 \paragraph{Singular Value Decomposition}
 
-Singular Value Decomposition (SVD) represents a powerful mathematical tool with extensive applications in data analysis \cite[, chapt. 1]{brunton22_data} and multivariable control systems where it is particularly valuable for analyzing directional properties in multivariable systems \cite{skogestad07_multiv_feedb_contr}.
+Singular Value Decomposition (SVD) represents a powerful mathematical tool with extensive applications in data analysis \cite[, chapt. 1]{brunton22_data} and multivariable control systems \cite{skogestad07_multiv_feedb_contr}, where it is particularly valuable for analyzing directional properties in multivariable systems.
 
 The SVD constitutes a unique matrix decomposition applicable to any complex matrix \(\bm{X} \in \mathbb{C}^{n \times m}\), expressed as:
 
@@ -991,8 +1012,8 @@ Additionally, the diagonal terms manifest as second-order dynamic systems, facil
 \end{figure}
 
 As it was surprising to obtain such a good decoupling at all frequencies, a variant system with identical dynamics but different sensor configurations was examined.
-Instead of using relative motion sensors collocated with the struts, three relative motion sensors were positioned as shown in Figure \ref{fig:detail_control_decoupling_model_test_alt}.
+Instead of using relative motion sensors aligned with the struts, three relative motion sensors were positioned as shown in Figure \ref{fig:detail_control_decoupling_model_test_alt}.
-Although Jacobian matrices could theoretically be used to map these sensors to the frame of the struts, application of the same SVD decoupling procedure yielded the plant response shown in Figure \ref{fig:detail_control_decoupling_svd_alt_plant}, which exhibits significantly greater coupling.
+Although Jacobian matrices could theoretically map between these different sensor arrangements, application of the same SVD decoupling procedure yielded the plant response shown in Figure \ref{fig:detail_control_decoupling_svd_alt_plant}, which exhibits significantly greater coupling.
 Notably, the coupling demonstrates local minima near the decoupling frequency, consistent with the fact that the decoupling matrices were derived specifically for that frequency point.
 
 \begin{figure}[htbp]
@@ -1035,7 +1056,8 @@ SVD decoupling generally results in a loss of physical meaning for the ``control
 The quality of decoupling achieved through these methods also exhibits distinct characteristics.
 Jacobian decoupling performance depends on the chosen reference frame, with optimal decoupling at low frequencies when aligned at the center of stiffness, or at high frequencies when aligned with the center of mass.
 Systems designed with coincident centers of mass and stiffness may achieve excellent decoupling using this approach.
-Modal decoupling offers good decoupling across all frequencies, though its effectiveness relies on the model accuracy, with discrepancies potentially resulting in significant off-diagonal elements.
+Modal decoupling offers good decoupling across all frequencies, though its effectiveness relies on the accuracy of the system model, with discrepancies potentially resulting in significant off-diagonal elements.
+The diagonal elements typically manifest as second-order low-pass filters, facilitating straightforward control design.
 SVD decoupling can be implemented using measured data without requiring a model, with optimal performance near the chosen decoupling frequency, though its effectiveness may diminish at other frequencies and depends on the quality of the real approximation of the response at the selected frequency point.
 
 \begin{table}[htbp]
@@ -1050,19 +1072,29 @@ SVD decoupling can be implemented using measured data without requiring a model,
 \midrule
 \textbf{Requirements} & Known geometry & Known equations of motion & Identified FRF\\
 \midrule
-\textbf{Decoupling Matrices} & Jacobian matrix \(\bm{J}_{\{O\}}\) & Eigenvectors \(\bm{\Phi}\) & SVD matrices \(\bm{U}\) and \(\bm{V}\)\\
+\textbf{Decoupling Matrices} & Decoupling using \(\bm{J}_{\{O\}}\) obtained from geometry & Decoupling using \(\bm{\Phi}\) obtained from modal decomposition & Decoupling using \(\bm{U}\) and \(\bm{V}\) obtained from SVD\\
 \midrule
 \textbf{Decoupled Plant} & \(\bm{G}_{\{O\}}(s) = \bm{J}_{\{O\}}^{-1} \bm{G}_{\mathcal{L}}(s) \bm{J}_{\{O\}}^{-\intercal}\) & \(\bm{G}_m(s) = \bm{\Phi}^{-1} \bm{G}_{\mathcal{X}}(s) \bm{\Phi}^{-\intercal}\) & \(\bm{G}_{\text{SVD}}(s) = \bm{U}^{-1} \bm{G}(s) \bm{V}^{-\intercal}\)\\
 \midrule
 \textbf{Controller} & \(\bm{K}_{\{O\}}(s) = \bm{J}_{\{O\}}^{-\intercal} \bm{K}_{d}(s) \bm{J}_{\{O\}}^{-1}\) & \(\bm{K}_m(s) = \bm{\Phi}^{-\intercal} \bm{K}_{d}(s) \bm{\Phi}^{-1}\) & \(\bm{K}_{\text{SVD}}(s) = \bm{V}^{-\intercal} \bm{K}_{d}(s) \bm{U}^{-1}\)\\
 \midrule
-\textbf{Interpretation} & Forces/Torques to Displacement/Rotation in chosen frame & Inputs (resp. outputs) to excite (resp. sense) individual modes & Directions of max to min controllability/observability\\
+\textbf{Interpretation} & Forces/Torques to Displacement/Rotation in chosen frame & Inputs to excite individual modes & Directions of max to min controllability/observability\\
+ &  & Output to sense individual modes & \\
 \midrule
-\textbf{Effectiveness} & Decoupling at low or high frequency depending on the chosen frame & Good decoupling at all frequencies & Good decoupling near the chosen frequency\\
+\textbf{Properties} & Decoupling at low or high frequency depending on the chosen frame & Good decoupling at all frequencies & Good decoupling near the chosen frequency\\
 \midrule
-\textbf{Pros} & Retain physical meaning of inputs / outputs. Controller acts on a meaningfully ``frame'' & Ability to target specific modes. Simple \(2^{nd}\) order diagonal plants & Good Decoupling near the crossover. Very General and requires no model\\
+\textbf{Pros} & Physical inputs / outputs & Target specific modes & Good Decoupling near the crossover\\
+ & Good decoupling at High frequency (diagonal mass matrix if Jacobian taken at the CoM) & 2nd order diagonal plant & Very General\\
+ & Good decoupling at Low frequency (if Jacobian taken at specific point) &  & \\
+ & Easy integration of meaningful reference inputs &  & \\
+ &  &  & \\
 \midrule
-\textbf{Cons} & Good decoupling at all frequency can only be obtained for specific mechanical architecture & Relies on the accuracy of equation of motions. Robustness to unmodelled dynamics may be poor & Loss of physical meaning of inputs /outputs. Decoupling away from the chosen frequency may be poor\\
+\textbf{Cons} & Coupling between force/rotation may be high at low frequency (non diagonal terms in K) & Need analytical equations & Loose the physical meaning of inputs /outputs\\
+ & Limited to parallel mechanisms (?) &  & Decoupling depends on the real approximation validity\\
+ & If good decoupling at all frequencies => requires specific mechanical architecture &  & Diagonal plants may not be easy to control\\
+\midrule
+\textbf{Applicability} & Parallel Mechanisms & Systems whose dynamics that can be expressed with M and K matrices & Very general\\
+ & Only small motion for the Jacobian matrix to stay constant &  & Need FRF data (either experimentally or analytically)\\
 \bottomrule
 \end{tabularx}
 \end{table}
@@ -1072,23 +1104,26 @@ SVD decoupling can be implemented using measured data without requiring a model,
 Once the system is properly decoupled using one of the approaches described in Section \ref{sec:detail_control_decoupling}, SISO controllers can be individually tuned for each decoupled ``directions''.
 Several ways to design a controller to obtain a given performance while ensuring good robustness properties can be implemented.
 
-In some cases ``fixed'' controller structures are utilized, such as PI and PID controllers, whose parameters are manually tuned \cite{furutani04_nanom_cuttin_machin_using_stewar,du14_piezo_actuat_high_precis_flexib,yang19_dynam_model_decoup_contr_flexib}.
+In some cases, ``fixed'' controller structures are utilized, such as PI and PID controllers \cite{furutani04_nanom_cuttin_machin_using_stewar,du14_piezo_actuat_high_precis_flexib,yang19_dynam_model_decoup_contr_flexib}.
+In such cases, the controller coefficients are manually tuned to obtain acceptable performance and robustness.
 
-Another popular method is Open-Loop shaping, which was used during the conceptual phase.
+Another popular method is Open-Loop shaping, that was used during the conceptual phase after the plan was decoupled in the frame of the struts.
-Open-loop shaping involves tuning the controller through a series of ``standard'' filters (leads, lags, notches, low-pass filters, \ldots{}) to shape the open-loop transfer function \(G(s)K(s)\) according to desired specifications, including bandwidth, gain and phase margins \cite[, chapt. 4.4.7]{schmidt20_desig_high_perfor_mechat_third_revis_edition}.
+The idea of open-loop shaping is to tune the controller (using a series of standard leads, lags, notches, low pass filters) such that the open-loop transfer function \(G(s)K(s)\) is made according to specification (i.e.
-Open-Loop shaping is very popular because the open-loop transfer function is a linear function of the controller, making it relatively straightforward to tune the controller to achieve desired open-loop characteristics.
+bandwidth, gain and phase margins, gain at a specific frequency, etc\ldots{}) \cite[, chapt. 4.4.7]{schmidt20_desig_high_perfor_mechat_third_revis_edition}.
-Another key advantage is that controllers can be tuned directly from measured frequency response functions of the plant without requiring an explicit model.
+Open-Loop shaping is very popular because the open-loop transfer function depends linearly on the controller, making it relatively straightforward to tune the controller to achieve desired open-loop characteristics.
+Another key advantage is that controllers can be tuned directly from measured frequency response functions without requiring an explicit plant model.
 
-However, the behavior (i.e. performance) of a feedback system is a function of closed-loop transfer functions.
+However, the behavior (i.e. performance) of a feedback system is a function of closed-loop transfer functions \cite[, chapt. 3]{skogestad07_multiv_feedb_contr}.
-Specifications can therefore be expressed in terms of the magnitude of closed-loop transfer functions, such as the sensitivity, plant sensitivity, and complementary sensitivity transfer functions \cite[, chapt. 3]{skogestad07_multiv_feedb_contr}.
+Specifications can therefore be expressed in terms of the magnitude of closed-loop transfer functions, such as the sensitivity, plant sensitivity, and complementary sensitivity transfer functions.
 With open-loop shaping, closed-loop transfer functions are changed only indirectly, which may make it difficult to directly address the specifications that are in terms of the closed-loop transfer functions.
 
-In order to synthesize a controller that directly shapes the closed-loop transfer functions (and therefore the performance metric), \(\mathcal{H}_\infty\text{-synthesis}\) may be used \cite{skogestad07_multiv_feedb_contr}.
+In order to synthesize a controller that directly shapes the closed-loop transfer functions (and therefore the performance metric), \(\mathcal{H}_\infty\) loop-shaping may be used \cite{skogestad07_multiv_feedb_contr}.
 This approach requires a good model of the plant and expertise in selecting weighting functions that will define the wanted shape of different closed-loop transfer functions \cite{bibel92_guidel_h}.
-\(\mathcal{H}_{\infty}\text{-synthesis}\) has been applied for the Stewart platform \cite{jiao18_dynam_model_exper_analy_stewar}, yet when benchmarked against more basic decentralized controllers, the performance gains proved small \cite{thayer02_six_axis_vibrat_isolat_system,hauge04_sensor_contr_space_based_six}.
+\(\mathcal{H}_{\infty}\) synthesis has been applied for the Stewart platform \cite{jiao18_dynam_model_exper_analy_stewar}, but comparative studies with more simple decentralized controllers did not show large improvements \cite{thayer02_six_axis_vibrat_isolat_system,hauge04_sensor_contr_space_based_six}.
 
 In this section, an alternative controller synthesis scheme is proposed in which complementary filters are used for directly shaping the closed-loop transfer functions (i.e., directly addressing the closed-loop performances).
-In Section \ref{ssec:detail_control_cf_control_arch}, the proposed control architecture is presented.
+
+In Section \ref{ssec:detail_control_cf_control_arch}, the proposed control architecture including the complementary filters is presented.
 In Section \ref{ssec:detail_control_cf_trans_perf}, typical performance requirements are translated into the shape of the complementary filters.
 The design of the complementary filters is briefly discussed in Section \ref{ssec:detail_control_cf_analytical_complementary_filters}, and analytical formulas are proposed such that it is possible to change the closed-loop behavior of the system in real time.
 Finally, in Section \ref{ssec:detail_control_cf_simulations}, a numerical example is used to show how the proposed control architecture can be implemented in practice.
@@ -1096,9 +1131,10 @@ Finally, in Section \ref{ssec:detail_control_cf_simulations}, a numerical exampl
 \label{ssec:detail_control_cf_control_arch}
 \paragraph{Virtual Sensor Fusion}
 
-The idea of using complementary filters in the control architecture originates from sensor fusion techniques \cite{collette15_sensor_fusion_method_high_perfor}, where two sensors are combined using complementary filters.
+The concept of using complementary filters in control architecture originates from sensor fusion techniques \cite{collette15_sensor_fusion_method_high_perfor}, where two sensors are combined using complementary filters.
 Building upon this concept, ``virtual sensor fusion'' \cite{verma20_virtual_sensor_fusion_high_precis_contr} replaces one physical sensor with a model \(G\) of the plant.
-The corresponding control architecture is illustrated in Figure \ref{fig:detail_control_cf_arch}, where \(G^\prime\) represents the physical plant to be controlled, \(G\) is a model of the plant, \(k\) is the controller, and \(H_L\) and \(H_H\) are complementary filters satisfying \(H_L(s) + H_H(s) = 1\).
+
+The control architecture is illustrated in Figure \ref{fig:detail_control_cf_arch}, where \(G^\prime\) represents the physical plant to be controlled, \(G\) is a model of the plant, \(k\) is the controller, and \(H_L\) and \(H_H\) are complementary filters satisfying \(H_L(s) + H_H(s) = 1\).
 In this arrangement, the physical plant is controlled at low frequencies, while the plant model is utilized at high frequencies to enhance robustness.
 
 \begin{figure}[htbp]
@@ -1124,14 +1160,14 @@ Consequently, this structure is mathematically equivalent to the single-loop arc
 When considering the extreme case of very high values for \(k\), the effective controller \(K(s)\) converges to the inverse of the plant model multiplied by the inverse of the high-pass filter, as expressed in \eqref{eq:detail_control_cf_high_k}.
 
 \begin{equation}\label{eq:detail_control_cf_high_k}
-  \lim_{k\to\infty} K(s) = \lim_{k\to\infty} \frac{k}{1+H_H(s) G(s) k} = \big( H_H(s) G(s) \big)^{-1}
+  \lim_{k\to\infty} K(s) = \lim_{k\to\infty} \frac{k}{1+H_H(s) G(s) k} = \left( H_H(s) G(s) \right)^{-1}
 \end{equation}
 
 If the resulting \(K\) is improper, a low-pass filter with sufficiently high corner frequency can be added to ensure its causal realization.
 Furthermore, for \(K\) to be stable, both \(G\) and \(H_H\) must be minimum phase transfer functions.
 
 With these assumptions, the resulting control architecture is illustrated in Figure \ref{fig:detail_control_cf_arch_class}, where the complementary filters \(H_L\) and \(H_H\) remain the only tuning parameters.
-The dynamics of this closed-loop system are described by equations \eqref{eq:detail_control_cf_cl_system_y} and \eqref{eq:detail_control_cf_cl_system_y}.
+The dynamics of this closed-loop system are described by \eqref{eq:detail_control_cf_sf_cl_tf_K_inf}.
 
 \begin{figure}[htbp]
 \centering
@@ -1146,7 +1182,7 @@ The dynamics of this closed-loop system are described by equations \eqref{eq:det
   \end{align}
 \end{subequations}
 
-At frequencies where the model accurately represents the physical plant (\(G^{-1} G^{\prime} \approx 1\)), the denominator simplifies to \(H_H + G^\prime G^{-1} H_L \approx H_H + H_L = 1\), and the closed-loop transfer functions are then described by equations \eqref{eq:detail_control_cf_cl_performance_y} and \eqref{eq:detail_control_cf_cl_performance_u}.
+At frequencies where the model accurately represents the physical plant (\(G^{-1} G^{\prime} \approx 1\)), the denominator simplifies to \(H_H + G^\prime G^{-1} H_L \approx H_H + H_L = 1\), and the closed-loop transfer functions are described by \eqref{eq:detail_control_cf_sf_cl_tf_K_inf_perfect}.
 
 \begin{subequations}\label{eq:detail_control_cf_sf_cl_tf_K_inf_perfect}
   \begin{alignat}{5}
@@ -1156,14 +1192,14 @@ At frequencies where the model accurately represents the physical plant (\(G^{-1
 \end{subequations}
 
 The sensitivity transfer function equals the high-pass filter \(S = \frac{y}{dy} = H_H\), and the complementary sensitivity transfer function equals the low-pass filter \(T = \frac{y}{n} = H_L\).
-Hence, when the plant model closely approximates the actual dynamics, the closed-loop transfer functions converge to the designed complementary filters, allowing direct translation of performance requirements into the design of the complementary.
+Hence, when the plant model closely approximates the actual system, the closed-loop behavior becomes fully determined by the designed complementary filters, enabling direct translation of performance requirements into filter design.
-\section{Translating the performance requirements into the shape of the complementary filters}
+\section{Translating the performance requirements into the shapes of the complementary filters}
 \label{ssec:detail_control_cf_trans_perf}
-Performance specifications in a feedback system can usually be expressed as upper bounds on the magnitudes of closed-loop transfer functions such as the sensitivity and complementary sensitivity transfer functions \cite{bibel92_guidel_h}.
+Performance specifications in feedback systems can be expressed as upper bounds on the magnitudes of closed-loop transfer functions such that the sensitivity \(|S(j\omega)|\) and complementary sensitivity \(|T(j\omega)|\) transfer functions \cite{bibel92_guidel_h}.
-The design of a controller \(K(s)\) to obtain the desired shape of these closed-loop transfer functions is known as closed-loop shaping.
+The design of a controller \(K(s)\) to achieve desired shapes of these closed-loop transfer functions is known as closed-loop shaping.
 
 In the proposed control architecture, the closed-loop transfer functions \eqref{eq:detail_control_cf_sf_cl_tf_K_inf} are expressed in terms of the complementary filters \(H_L(s)\) and \(H_H(s)\) rather than directly through the controller \(K(s)\).
-Therefore, performance requirements must be translated into constraints on the shape of these complementary filters.
+Therefore, performance requirements must be translated into constraints on the shapes of these complementary filters.
 \paragraph{Nominal Stability (NS)}
 A closed-loop system is stable when all its elements (here \(K\), \(G^\prime\), and \(H_L\)) are stable and the sensitivity function \(S = \frac{1}{1 + G^\prime K H_L}\) is stable.
 For the nominal system (\(G^\prime = G\)), the sensitivity transfer function equals the high-pass filter: \(S(s) = H_H(s)\).
@@ -1173,7 +1209,6 @@ Consequently, stable and minimum phase complementary filters must be employed.
 \paragraph{Nominal Performance (NP)}
 
 Performance specifications can be formalized using weighting functions \(w_H\) and \(w_L\), where performance is achieved when \eqref{eq:detail_control_cf_weights} is satisfied.
-The weighting functions define the maximum magnitude of the closed-loop transfer functions as a function of frequency, effectively determining their ``shape''.
 
 \begin{subequations}\label{eq:detail_control_cf_weights}
   \begin{align}
@@ -1182,7 +1217,7 @@ The weighting functions define the maximum magnitude of the closed-loop transfer
   \end{align}
 \end{subequations}
 
-For the nominal system, \(S = H_H\) and \(T = H_L\), hence the performance specifications can be converted on the shape of the complementary filters \eqref{eq:detail_control_cf_nominal_performance}.
+For the nominal system, where \(S = H_H\) and \(T = H_L\), nominal performance is ensured by satisfying \eqref{eq:detail_control_cf_nominal_performance}.
 
 \begin{equation}\label{eq:detail_control_cf_nominal_performance}
 \Aboxed{\text{NP} \Longleftrightarrow {\begin{cases*}
@@ -1191,19 +1226,22 @@ For the nominal system, \(S = H_H\) and \(T = H_L\), hence the performance speci
   \end{cases*}}}
 \end{equation}
 
+Typical performance requirements can therefore be translated into constraints on the complementary filters.
 For disturbance rejection, the magnitude of the sensitivity function \(|S(j\omega)| = |H_H(j\omega)|\) should be minimized, particularly at low frequencies where disturbances are usually most prominent.
 Similarly, for noise attenuation, the magnitude of the complementary sensitivity function \(|T(j\omega)| = |H_L(j\omega)|\) should be minimized, especially at high frequencies where measurement noise typically dominates.
+The closed-loop bandwidth can be effectively limited by ensuring that \(|T(j\omega)|\) remains below \(\frac{1}{\sqrt{2}}\) at frequencies above the maximum desired bandwidth.
+By carefully selecting the shapes of these complementary filters, nominal performance specifications can be directly addressed in an intuitive manner.
+
 Classical stability margins (gain and phase margins) are also related to the maximum amplitude of the sensitivity transfer function.
 Typically, maintaining \(|S|_{\infty} \le 2\) ensures a gain margin of at least 2 and a phase margin of at least \(\SI{29}{\degree}\).
-
-Therefore, by carefully selecting the shape of the complementary filters, nominal performance specifications can be directly addressed in an intuitive manner.
 \paragraph{Robust Stability (RS)}
 
 Robust stability refers to a control system's ability to maintain stability despite discrepancies between the actual system \(G^\prime\) and the model \(G\) used for controller design.
 These discrepancies may arise from unmodeled dynamics or nonlinearities.
 
 To represent these model-plant differences, input multiplicative uncertainty as illustrated in Figure \ref{fig:detail_control_cf_input_uncertainty} is employed.
-The set of possible plants \(\Pi_i\) is described by \eqref{eq:detail_control_cf_multiplicative_uncertainty}, with the weighting function \(w_I\) selected such that all possible plants \(G^\prime\) are contained within the set \(\Pi_i\).
+The set of possible plants \(\Pi_i\) is described by \eqref{eq:detail_control_cf_multiplicative_uncertainty}.
+With the weighting function \(w_I\) selected such that all possible plants \(G^\prime\) are contained within the set \(\Pi_i\).
 
 \begin{equation}\label{eq:detail_control_cf_multiplicative_uncertainty}
   \Pi_i: \quad G^\prime(s) = G(s)\big(1 + w_I(s)\Delta_I(s)\big); \quad |\Delta_I(j\omega)| \le 1 \ \forall\omega
@@ -1238,7 +1276,8 @@ After algebraic manipulation, robust stability is guaranteed when the low-pass c
 \end{equation}
 \paragraph{Robust Performance (RP)}
 
-Robust performance ensures that performance specifications \eqref{eq:detail_control_cf_weights} are met even when the plant dynamics fluctuates within specified bounds \eqref{eq:detail_control_cf_robust_perf_S}.
+Robust performance ensures that performance specifications \eqref{eq:detail_control_cf_weights} are met even as plant dynamics varies within specified bounds.
+This requires the performance condition to be valid for all possible plants in the defined uncertainty set \(\Pi_i\):
 
 \begin{equation}\label{eq:detail_control_cf_robust_perf_S}
   \text{RP} \Longleftrightarrow |w_H(j\omega) S(j\omega)| \le 1 \quad \forall G^\prime \in \Pi_I, \ \forall\omega
@@ -1256,8 +1295,8 @@ Therefore, for SISO systems, ensuring robust stability and nominal performance i
 \section{Complementary filter design}
 \label{ssec:detail_control_cf_analytical_complementary_filters}
 
-As proposed in Section \ref{sec:detail_control_sensor}, complementary filters can be shaped using standard \(\mathcal{H}_{\infty}\text{-synthesis}\) techniques.
+As proposed in Section \ref{sec:detail_control_sensor}, complementary filters can be shaped using standard \(\mathcal{H}_{\infty}\) synthesis techniques.
-This approach is particularly well-suited since performance requirements were expressed as upper bounds on the magnitude of the complementary filters.
+This approach is particularly well-suited since performance requirements were expressed as upper bounds on the magnitude of the complementary filters (Section \ref{ssec:detail_control_cf_trans_perf}).
 
 Alternatively, analytical formulas for complementary filters may be employed.
 For some applications, first-order complementary filters as shown in Equation \eqref{eq:detail_control_cf_1st_order} are sufficient.
@@ -1278,7 +1317,7 @@ These filters can be transformed into the digital domain using the Bilinear tran
   \end{align}
 \end{subequations}
 
-A significant advantage of using analytical formulas for complementary filters is that key parameters such as \(\omega_0\) can be tuned in real-time, as illustrated in Figure \ref{fig:detail_control_cf_arch_tunable_params}.
+A significant advantage of using analytical formulas for complementary filters is that key parameters such as \(\omega_0\) can be modified in real-time, as illustrated in Figure \ref{fig:detail_control_cf_arch_tunable_params}.
 This real-time tunability allows rapid testing of different control bandwidths to evaluate performance and robustness characteristics.
 
 \begin{figure}[htbp]
@@ -1289,7 +1328,7 @@ This real-time tunability allows rapid testing of different control bandwidths t
 
 For many practical applications, first order complementary filters are not sufficient.
 Specifically, a slope of \(+2\) at low frequencies for the sensitivity transfer function (enabling accurate tracking of ramp inputs) and a slope of \(-2\) for the complementary sensitivity transfer function are often desired.
-For these cases, the complementary filters analytical formula in Equation \eqref{eq:detail_control_cf_2nd_order} is proposed.
+For these cases, the second-order complementary filters presented in Equation \eqref{eq:detail_control_cf_2nd_order} are proposed.
 
 \begin{subequations}\label{eq:detail_control_cf_2nd_order}
   \begin{align}
@@ -1299,9 +1338,12 @@ For these cases, the complementary filters analytical formula in Equation \eqref
 \end{subequations}
 
 The influence of parameters \(\alpha\) and \(\omega_0\) on the frequency response of these complementary filters is illustrated in Figure \ref{fig:detail_control_cf_analytical_effect}.
-The parameter \(\alpha\) primarily affects the damping characteristics near the crossover frequency as well as high and low frequency magnitudes, while \(\omega_0\) determines the frequency at which the transition between high-pass and low-pass behavior occurs.
+The parameter \(\alpha\) primarily affects the damping characteristics near the crossover frequency, while \(\omega_0\) determines the frequency at which the transition between high-pass and low-pass behavior occurs.
 These filters can also be implemented in the digital domain with analytical formulas, preserving the ability to adjust \(\alpha\) and \(\omega_0\) in real-time.
 
+The presented analytical formulations offer an attractive balance between design simplicity and performance.
+This capability to tune parameters in real-time is particularly valuable during commissioning of the controller.
+
 \begin{figure}[htbp]
 \begin{subfigure}{0.48\textwidth}
 \begin{center}
@@ -1319,17 +1361,18 @@ These filters can also be implemented in the digital domain with analytical form
 \end{figure}
 \section{Numerical Example}
 \label{ssec:detail_control_cf_simulations}
-To implement the proposed control architecture in practice, the following procedure is proposed:
+To systematically apply the proposed control technique, the following procedure is recommended:
 
 \begin{enumerate}
 \item Identify the plant to be controlled to obtain the plant model \(G\).
-\item Design the weighting function \(w_I\) such that all possible plants \(G^\prime\) are contained within the uncertainty set \(\Pi_i\).
+\item Design the weighting function \(w_I\) such that all possible plants \(G^\prime\) are contained in the uncertainty set \(\Pi_i\).
 \item Translate performance requirements into upper bounds on the complementary filters as explained in Section \ref{ssec:detail_control_cf_trans_perf}.
 \item Design the weighting functions \(w_H\) and \(w_L\) and generate the complementary filters using \(\mathcal{H}_{\infty}\text{-synthesis}\) as described in Section \ref{ssec:detail_control_sensor_hinf_method}.
 If the synthesis fails to produce filters satisfying the defined upper bounds, either revise the requirements or develop a more accurate model \(G\) that will allow for a smaller \(w_I\).
 For simpler cases, the analytical formulas for complementary filters presented in Section \ref{ssec:detail_control_cf_analytical_complementary_filters} can be employed.
 \item If \(K(s) = H_H^{-1}(s) G^{-1}(s)\) is not proper, add low-pass filters with sufficiently high corner frequencies to ensure realizability.
 \end{enumerate}
+\paragraph{Plant}
 
 To evaluate this control architecture, a simple test model representative of many synchrotron positioning stages is utilized (Figure \ref{fig:detail_control_cf_test_model}).
 In this model, a payload with mass \(m\) is positioned on top of a stage.
@@ -1342,11 +1385,13 @@ The positioning stage itself is characterized by stiffness \(k\), internal dampi
 The model of the plant \(G(s)\) from actuator force \(F\) to displacement \(y\) is described by Equation \eqref{eq:detail_control_cf_test_plant_tf}.
 
 \begin{equation}\label{eq:detail_control_cf_test_plant_tf}
-  G(s) = \frac{1}{m s^2 + c s + k}, \quad m = \SI{20}{\kg},\ k = 1\si{\N/\mu\m},\ c = 10^2\si{\N\per(\m\per\s)}
+  G(s) = \frac{1}{m s^2 + c s + k}
 \end{equation}
 
-The plant dynamics include uncertainties related to limited support compliance, unmodeled flexible dynamics and payload dynamics.
+The parameter values are set to \(m = \SI{20}{\kg}\), \(k = 1\si{\N/\mu\m}\), and \(c = 10^2\si{\N\per(\m\per\s)}\).
-These uncertainties are represented using a multiplicative input uncertainty weight \eqref{eq:detail_control_cf_test_plant_uncertainty}, which specifies the magnitude of uncertainty as a function of frequency.
+
+The plant dynamics include uncertainties related to limited support compliance, unmodeled flexible dynamics, payload dynamics, and other factors.
+These uncertainties are represented using a multiplicative input uncertainty weight \eqref{eq:detail_control_cf_test_plant_uncertainty}., which specifies the magnitude of uncertainty as a function of frequency:
 
 \begin{equation}\label{eq:detail_control_cf_test_plant_uncertainty}
   w_I(s) = 10 \cdot \frac{(s+100)^2}{(s+1000)^2}
@@ -1371,10 +1416,10 @@ Figure \ref{fig:detail_control_cf_bode_plot_mech_sys} illustrates both the nomin
 \end{figure}
 \paragraph{Requirements and choice of complementary filters}
 
-As discussed in Section \ref{ssec:detail_control_cf_trans_perf}, nominal performance requirements can be expressed as upper bounds on the shape of the complementary filters.
+As discussed in Section \ref{ssec:detail_control_cf_trans_perf}, nominal performance requirements can be expressed as upper bounds on the shapes of the complementary filters.
 For this example, the requirements are:
 \begin{itemize}
-\item track ramp inputs (i.e. constant velocity scans) with zero steady-state error: a \(+2\) slope at low frequencies for the magnitude of the sensitivity function \(|S(j\omega)|\) is required
+\item to track ramp inputs (constant velocity scans) with zero steady-state error, which necessitates a \(+2\) slope at low frequencies for the magnitude of the sensitivity function \(|S(j\omega)|\)
 \item filtering of measurement noise above \(\SI{300}{Hz}\), where sensor noise is significant (requiring a filtering factor of approximately 100 above this frequency)
 \item maximizing disturbance rejection
 \end{itemize}
@@ -1385,9 +1430,8 @@ This condition is satisfied when the magnitude of the low-pass complementary fil
 Robust performance is achieved when both nominal performance and robust stability conditions are simultaneously satisfied.
 
 All requirements imposed on \(H_L\) and \(H_H\) are visualized in Figure \ref{fig:detail_control_cf_specs_S_T}.
-While \(\mathcal{H}_\infty\text{-synthesis}\) could be employed to design the complementary filters, analytical formulas were used for this relatively simple example.
+While \(\mathcal{H}_\infty\) synthesis could be employed to design the complementary filters, analytical formulas were used for this relatively simple example.
-The second-order complementary filters from Equation \eqref{eq:detail_control_cf_2nd_order} were selected with parameters \(\alpha = 1\) and \(\omega_0 = 2\pi \cdot 20\,\text{Hz}\).
+Specifically, the second-order complementary filters from Equation \eqref{eq:detail_control_cf_2nd_order} were selected, providing the desired \(+2\) and \(-2\) slopes, with parameters \(\alpha = 1\) and \(\omega_0 = 2\pi \cdot 20\) Hz.
-There magnitudes are displayed in Figure \ref{fig:detail_control_cf_specs_S_T}, confirming that these complementary filters are fulfilling the specifications.
 
 \begin{figure}[htbp]
 \begin{subfigure}{0.48\textwidth}
@@ -1448,7 +1492,7 @@ In this section, a control architecture in which complementary filters are used
 This approach differs from traditional open-loop shaping in that no controller is manually designed; rather, appropriate complementary filters are selected to achieve the desired closed-loop behavior.
 The method shares conceptual similarities with mixed-sensitivity \(\mathcal{H}_{\infty}\text{-synthesis}\), as both approaches aim to shape closed-loop transfer functions, but with notable distinctions in implementation and complexity.
 
-While \(\mathcal{H}_{\infty}\text{-synthesis}\) offers greater flexibility and can be readily generalized to MIMO plants, the presented approach provides a simpler alternative that requires minimal design effort.
+While \(\mathcal{H}_{\infty}\text{-synthesis}\) synthesis offers greater flexibility and can be readily generalized to MIMO plants, the presented approach provides a simpler alternative that requires minimal design effort.
 Implementation only necessitates extracting a model of the plant and selecting appropriate analytical complementary filters, making it particularly interesting for applications where simplicity and intuitive parameter tuning are valued.
 
 Due to time constraints, an extensive literature review comparing this approach with similar existing architectures, such as Internal Model Control \cite{saxena12_advan_inter_model_contr_techn}, was not conducted.
@@ -1458,21 +1502,5 @@ The control architecture has been presented for SISO systems, but can be applied
 It will be experimentally validated with the NASS during the experimental phase.
 \chapter*{Conclusion}
 \label{sec:detail_control_conclusion}
-
-In order to optimize the control of the Nano Active Stabilization System, several aspects of control theory were studied.
-Different approaches to combine sensors were compared in Section \ref{sec:detail_control_sensor}.
-While High Authority Control-Low Authority Control (HAC-LAC) was successfully applied during the conceptual design phase, the focus of this work was extended to sensor fusion techniques where two or more sensors are combined using complementary filters.
-It was demonstrated that the performance of such fusion depends significantly on the magnitude of the complementary filters.
-To address this challenge, a synthesis method based on \(\mathcal{H}_\infty\text{-synthesis}\) was proposed, allowing for intuitive shaping of the complementary filters through weighting functions.
-For the NASS, while HAC-LAC remains a natural way to combine sensors, the potential benefits of sensor fusion merit further investigation.
-
-Various decoupling strategies for parallel manipulators were examined in Section \ref{sec:detail_control_decoupling}, including decentralized control, Jacobian decoupling, modal decoupling, and Singular Value Decomposition (SVD) decoupling.
-The main characteristics of each approach were highlighted, providing valuable insights into their respective strengths and limitations.
-Among the examined methods, Jacobian decoupling was determined to be most appropriate for the NASS, as it provides straightforward implementation while preserving the physical meaning of inputs and outputs.
-
-With the system successfully decoupled, attention shifted to designing appropriate SISO controllers for each decoupled direction.
-A control architecture for directly shaping closed-loop transfer functions was proposed.
-It is based on complementary filters that can be designed using either the proposed \(\mathcal{H}_\infty\text{-synthesis}\) approach described earlier or through analytical formulas.
-Experimental validation of this method on the NASS will be conducted during the experimental tests on ID31.
 \printbibliography[heading=bibintoc,title={Bibliography}]
 \end{document}